Synthetic Aperture Gps Signal Processing

Synthetic Aperture GPS Signal Processing DoD Photo by MSGT Paul N. Hayashi

Concept and Feasibility Demonstration

Most people relate to GNSS as a technology for positioning, navigation, and timing. However, space weather researchers have already demonstrated the use of GPS as a useful sensor for studies of the Earth’s atmosphere. This article introduces the concept of applying synthetically generated, phased-array antennas for processing GPS signals to create large antenna apertures. In turn, the narrow-beam generation capabilities of synthetic apertures can be used to mitigate interference and jamming and for producing high-resolution radar images passively using received GPS signals — which raise the possibility of some interesting civil and military applications. Andrey Soloviev University of Florida Frank van Graas, Sanjeev Gunawardena Ohio University Mikel Miller Air Force Research Laboratory

Aerial view of a transportererector-launcher vehicle covered with camouflage netting, during ground launch cruise missile (GLCM) evaluation.

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ynthetic aperture techniques combine data obtained from multiple sensors — or one sensor moving among multiple locations, or both — to construct a single image. These techniques have been widely researched, developed, and applied in the area of radar systems. This article discusses efforts to extend synthetic aperture concepts to GPS signal processing, exploiting the beam steering capabilities of synthetically generated phased array antennas. In it, we will describe the fast Fourier transform (FFT)–based method used to simultaneously steer a synthetic array’s beams in multiple directions. We will also discuss the results of simulator and m ay/ june 200 9

flight tests to demonstrate the efficacy of synthetic beam steering techniques for GPS antennas. Development of GPS-based SARs will enable high-resolution imaging capabilities using passive receivers of GPS signals and allow 24-hour global availability of imaging technology. It represents a dual-use technology that could support military applications such as imaging of military ground fleet hidden under foliage, as well as humanitarian applications such as detection of unexploded ordnance.

GPS SAR: The Concept

Large synthetic apertures allow for producing very narrow array beams. These InsideGNSS

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synthetic aperture

Synthetic beam steering (interference and jamming mitigation) GPS satellite

Jammer

Antenna beam

Synthetic aperture GPS signal processing FIGURE 1

GPS-based synthetic aperture radar (passive imaging) Synthetic aperture GPS signal processing

GPS satellite

Antenna beam

Applications of synthetic aperture GPS signal processing

narrow beams are steered in desired 1 d i rec t ions usi ng Antenna beam δθ~ N GPS signal processing techniques. θ0 d d As shown in Figphase delay phase delay phase delay ure 1, an array beam d cos(θ0) 2d cos(θ0) Nd cos(θ0) can be steered in the direction of a GPS Antenna satellite to mitigate output the effects of radio FIGURE 2 Beam steering with a one-dimensional phased array: phase delays are applied frequency interference and jamming to individual antenna outputs to steer the beam in the direction of θ0, the beam width is signals that are originversely proportional to the number of array inating from direcelements (N) tions other than the satellite. Steering the array beam towards reflecting objects to record high-resolution radar images provides the foundation for the development of GPS-based synthetic aperture radars (SARs). An important consideration in using GPS-based SAR is that large synthetic arrays are generated with small physical antennas utilizing platform motion and/or multiplatform integration. As a result, the physical size of the antenna does not act as a limiting factor. This, in turn, enables miniaturization of the technology for applications on small platforms such as mini-autonomous aerial vehicles (UAVs) and microUAVs. Phased array antennas have been widely employed for antenna beam steering. In a phased array, phases of individual antennas are adjusted to maximize the array gain in a desired direction, while increasing the array size narrows the array beamwidth. Figure 2 illustrates beam steering in the case of a one-dimensional (1D) array. In the GPS domain, beam-steering techniques — both analog beam steering and digital — have primarily been exploited to mitigate interference.

Hardware versus Software GPS

In designing our phased array, we needed to decide whether to implement an architecture with a hardware or software GPS receiver. 38

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A hardware-based construction has several limitations. For instance, an increase in the physical size of the array is required to narrow its beamwidth. Moreover, adjusting the phases of individual antennas in hardware constrains the system’s capability to simultaneously generate multiple beams that can be used, for example, to track multiple satellites or to simultaneously track both direct and reflected (multipath) signals. To overcome these limitations, we propose a synthetic array generation scheme that uses a software GPS receiver architecture. Instead of adding new antennas to the array, the beam is narrowed by exploiting antenna motion — that is, the array is synthesized by observing an antenna at different locations over time. Figure 3 and Figure 4 illustrate this principle for 1D and two-dimensional (2D) array cases, respectively. Generation of synthetic GPS antenna arrays is conceptually similar to synthetic aperture radar, where antenna motion is Incoming GPS signal S(t) d

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Synthetic generation of a one-dimensional phased array: an incoming GPS signal is down-sampled by the GPS receiver RF front-end; signal samples that correspond to different spatial antenna locations are combined to generate a synthetic phased array; phases of individual samples are adjusted to steer the array’s beam in the direction of the incident angle of the GPS satellite signal θ0. FIGURE 3

d

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RF front-end

Phased array signal processing

Synthetic generation of a two-dimensional phased array: Physical one-dimensional (1D) arrays are used to steer the beam in the first dimension (beam direction is collinear to the planar surface that is perpendicular to the direction of platform motion); 1D arrays at different spatial locations are applied for beam steering in the second dimension (beam direction is collinear to the planar surface that is parallel to the direction of motion); measurements of individual antennas are combined for phased array processing. Note that the 1D physical antenna arrays can be implemented on a single platform or can exploit multi-platform implementations such as multiple autonomous aerial vehicles (UAVs). FIGURE 4

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used to increase the antenna aperture in order to increase the azimuth resolution. The synthetic array generation needs to operate with signal samples. In particular, samples that are taken a certain distance apart (generally, a half-wavelength apart: d=λ/2) must be combined. Hence, we use a software-defined GPS receiver to generate a synthetic phased array antenna. The software receiver approach also allows the generation of multiple beams that are steered in different directions. Instead of hardware phase adjustments, a phase of a signal sample is adjusted to maximize the gain in a given direction (as seen in Figure 3). As a result, multiple beams can be generated simultaneously by applying different sequences of phase shifts to the same set of signal samples. This simultaneous steering in different directions can be used, for example, for simultaneous tracking of direct and reflected signals such as urban and ground multipath reflections. In the remainder of this article, we will first summarize previous efforts in the area of synthetic aperture GPS signal processing. Then we will discuss the principles of FFT-based multi-directional beam steering and how we applied them to develop signal processing techniques for synthetic phased array GPS antennas. Finally, we describe the simulation and live data test results used to verify the beam steering methods that we have developed. In particular, we apply actual flight data and ground data to demonstrate the operation of 1D and 2D synthetic phased GPS antenna arrays. Simulated data are exploited to demonstrate the use of 2D synthetic phased arrays for simultaneous tracking of direct and multipath signals. We also use simulated data to demonstrate GPSbased SAR imaging.

Earlier Work

The concept of synthetic aperture signal processing for GNSS signals has been previously considered in both the navigation domain, and in the area of radar www.insidegnss.com

systems. (For a discussion of the former principle, see in particular the papers by A. Broumandan et alia, S. Draganov et alia, and T. Pany et alia cited in the Additional Resources section near the end of this article. For a discussion of the latter, see the paper by M. Cherniakov et alia.) In the navigation domain, these earlier papers describe synthetic aperture GPS signal processing for a single antenna case as well as the exploitation of circular antenna motion to synthesize a circular phased array. In the work described by A. Broumandan et alia, a synthetic phased array is applied for interference mitiga-

efficient 2D FFT-based signal processing algorithm to simultaneously steer the array beam in multiple directions. As suggested previously, the array beam can be steered towards reflecting objects to record high-resolution SAR images with GPS signals. For GPS-based SAR, the range-based resolution of the cross-track image component is limited by the duration of the chip of the pseudorandom ranging sequence: 300 meters for the C/A-code and 30 meters for the GPS P-code. Focusing the array beam using multiple antennas that are mounted perpendicular to the direction of motion to resolve the cross-track component

Focusing the array beam using multiple antennas that are mounted perpendicular to the direction of motion to resolve the cross-track component improves the cross-track image resolution beyond the C/A or Pcode chip duration. tion while the paper by T. Pany et alia discusses the application of the circular synthetic array to suppress multipath. S. Draganov et alia discuss the use of the synthetic aperture technique by the ultra-tightly coupled GNSS/INS architecture to mitigate multipath. In their paper, Cherniakov et alia discuss the use of GLONASS signals from the Russian GNSS system as signals of opportunity for bi-static synthetic aperture imaging. There, antenna motion is utilized to achieve high-resolution imaging capabilities in the direction of motion. The cross-track resolution is achieved through use of the GLONASS precision (P)-code, based on publicly available technical specifications, which provides a ranging resolution of about 30 meters. This article extends synthetic aperture GPS signal processing for those cases in which multiple GPS antennas are used. Antenna motion is used to synthesize one-dimensional phased arrays. As indicated in Figure 4, the second dimension is added (synthesized) through the combining of signals received by multiple antennas mounted perpendicular to the direction of motion. We will introduce a computationally m ay/ june 200 9

improves the cross-track image resolution beyond the C/A or P-code chip duration. The approach especially benefits cases where the multiplatform signal integration can be applied to construct large array apertures in the cross-track direction.

FFT-Based Multi-Directional Beam Steering

As reported by M. I. Skolnik (see Additional Resources), FFT-based multidirectional beam steering techniques have been previously employed for radar applications. In our work described here, we adopted these techniques to develop computationally efficient methods for multi-directional beam steering of synthetic GPS antenna arrays. The FFT-based beam steering technique processes synthetic phased array data to construct a GPS signal image in which each image pixel contains signal parameter information corresponding to a signal that is received from a particular steering angle. Figure 5 illustrates the FFT-based signal image construction for the 2D antenna array. Each cell of the 2D FFT frequency grid corresponds to a particular 2D steering angle, where the corresponInsideGNSS

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synthetic aperture Signal image Normalized signal power

where R is the absolute value of the distance between the current antenna and the first antenna of the array. For the physical array case, R is the distance between antennas:

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In (2), m is the antenna index number within the array (starting with index zero for the first antenna) and d is the distance between two adjacent antennas (see Figure 2). For the synthetic array case, R is the antenna displacement, as follows:

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where R is the displacement vector and || is the absolute value. Beam steering is performed by multiplying samples S of the incoming signal by a complex exponential: The array output is then formed by adding individual antenna outputs:

FFT frequency grid FFT-based multi-directional beam steering: In this simulation, a 2D GPS signal image contains the received direct signal and a multipath reflection; each image pixel corresponds to a particular 2D steering angle derived from the FFT frequency grid; multiple signal sources (such as direct and multipath signals) can be identified and processed based on the signal image. FIGURE 5

dence between frequency and angles is defined by the antenna size and FFT parameters. (We will present detailed equations later in this section.) Essentially, the FFT-based approach provides a signal image that is similar to the one constructed by a digital photographic camera: each “pixel” in the image is defined by the “intensity” of the signal that is received from the angular direction associated with this pixel. In the case of multi-directional beam steering, the “pixel intensity” is represented by a post-correlation complex amplitude that contains the in-phase (I) value (real part of the complex amplitude) and quadrature (Q) value (imaginary part of the complex amplitude). This signal image can be used to identify and process multiple signal sources that may include direct signals, interference signals, and multipath reflections. Hence, this image can be applied to simultaneously track multiple signal sources such as direct signal and multipath reflections. The following section describes the principles of FFT-based multi-directional beam steering for synthetic GPS antenna arrays.

FFT for Multi-Directional Beam Steering

To steer a phased array in the angular direction of θ0 (see Figure 2), phases of individual antennas are adjusted by Δφ, which is defined as follows: 40

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In (5), Sm is the output of the mth antenna, M is the number of antennas in the array, and d=λ/2 is normally chosen to avoid beam ambiguities (i.e., a creation of multiple beams in the angular range from 0 to 180 degrees). For d=λ/2, equation (5) is modified as follows:

The antenna beam can be steered simultaneously in multiple directions if we use the FFT mechanism to implement equation (6). FFT harmonic frequencies can be chosen to satisfy the desired steering angular range and angular resolution. For the case of a physical antenna array, the use of the FFT instead of summation transforms single-direction steering into multi-directional steering as follows:

where {θk} are steering angles and k is the FFT frequency index. Note that k is changing from 0 to M/2 and not from 0 to M-1. This is due to the fact that the FFT spectrum amplitudes with the index numbers M/2+1 to M are complex conjugates of the spectrum amplitudes with the index numbers 1 to M/2-1. Consequently, the former do not provide any new information and are not considered.

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From equations (6) and (7), the FFT spectrum amplitude for the kth frequency harmonic is defined as follows:

Signal samples

d

d

FFT1 FFT2 FFTP

FIGURE 6

On the other hand, this spectrum amplitude can be related to the amplitude of the phased array that is steered in the direction of θk:

From equations (8) and (9):

or:

Equation (11) defines mapping of the FFT frequencies into steering angles for multi-directional beam steering. Thus, the FFT that is applied to outputs of individual antennas generates multiple beams that are steered in different directions. These steering directions are defined by the initial steering angle θ0 and FFT harmonic frequencies as specified by equation (11). To steer multiple beams within the angular range from 0 to 180 degrees, the FFT is first applied for θ0 = 0

This provides beam steering in the angular range from 0 to 90 degrees. To extend the steering angles to the range from 90 to 180 degrees, the second FFT is applied for θ0 = π/2

Synthetic array output

FFT-based beam steering for the synthetic array case

FFT-Based Synthetic Beam Steering for GPS Antennas

Figure 6 illustrates an FFT-based multi-direction beam steering

method for the synthetic array case. First, batches of signal samples are formed in such a way that the spatial distance between first samples in the adjacent batches is d. Second, FFTs are applied to samples that have the same index number within different batches: for example, to first samples of each batch, second samples of each batch, and so on. The total number of FFTs required equals P; where P is the number of samples in the batch. Third, FFT results are added together to improve the signal-to-noise ratio (SNR) for the received GPS signal. The FFT addition operation in the synthetic array case is equivalent to the incoming/replica signal correlation in the conventional GPS receiver architecture. Addition of FFT outputs forms the output of the synthetic phased array. To reduce the computational load, the number of signal samples in the batch can be reduced using averaging. In cases where P≥4 and d=λ/2, distortions associated with this averaging have negligible influence on the FFT-based multi-directional beam steering. We should note that GPS carrier phase tracking must be maintained for phased array antenna formation. Coherent signal accumulation over the entire synthetic aperture is required to maintain carrier phase tracking capabilities. To support coherent signal accumulation, down-sampled GPS signals must be compensated for changes in the carrier phase due to intermediate frequency (IF) variations and satellite motion as well as for changes in the code phase of the pseudorandom code sequence (PRN). Equation (15) provides the corresponding compensation expression for satellite j:

Hence, a complete FFT-based multi-direction beam steering procedure combines FFT outputs for initial steering angles of 0 and 90 degrees:

where: tn is the discrete time within the current aperture accumulation interval: , tn = t0 + n • Δt, Δt is the time discrete of GPS signal down-sampling; www.insidegnss.com

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f IF is the intermediate frequency, which is the frequency of down-conversion of the incoming GPS signal to baseband; ΔR SV (t n) is the increment in the satellite/receiver range (or j the line-of-sight — LOS — increment) that is due to satellite motion; λL is the wavelength of the GPS Link 1 (L1) carrier; 1 PRNj is the PRN for satellite j; and, is the estimate of the code phase at the start of the aperture accumulation, where early, prompt or late code phase estimates can be used. Equation (16) is applied to compute the ΔRSV term:

Normalized energy

synthetic aperture

j

FIGURE 7

In (16), (. , .) is the vector dot product, ej is the satellite/ receiver LOS unit vector, R SV is the satellite position vector; j and Rrcvr is the receiver position vector. Note that equation (16) does not compensate the PRN code phase for antenna motion. Synthetic apertures stay in the range from 1.2 to 6.2 meters for experimental scenarios reported in this article (see next section), which focuses on GPS C/A code applications. In this case, because the antenna aperture is significantly shorter that the code chip length (equivalent to approximately 300 meters), the signal-to-noise ratio (SNR) processing loss caused by uncompensated antenna motion is negligible (less than 0.2 dB). For apertures that are comparable to the length of the C/Acode chip or for precision (P–code) applications where the chip duration is equivalent to approximately 30 meters, changes in the code phase resulting from antenna motion must be taken into account. Future research will address modifications of synthetic aperture algorithms that account for code phase changes due to antenna motion. Note that antenna motion must be compensated for the construction of the synthetic antennas as detailed in the next section. Navigation message data bits in the GPS signal must be wiped-off to avoid energy losses due to bit transitions for those cases where the time duration of synthetic aperture exceeds the duration of navigation data bits (20 milliseconds). The bit wipeoff can utilize bit estimates from GPS receiver tracking loops. Alternatively, an energy-based bit estimation algorithm described in a forthcoming article by A. Soloviev et alia (see Additional Resources) or Kalman filter bit estimation routines (see the articles by N. I. Zeidan et alia and M. L. Psiaki et alia in Additional Resources) can be used for those cases where low carrier-to-noise ratio (C/N0) signals are processed. To determine the spatial distance between signal samples we used the motion trajectory computed by an inertial navigation system (INS). We applied a quarter-wavelength spatial separation between synthetic antennas to the methods reported in this article (see Equation [21] below). This separation corresponds to approximately five centimeters for the GPS L1 car42

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1 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0

Array pattern for 12 antennas SV LOS angle Physical array pattern Synthetic array pattern (sync function)

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rier. Thus, the INS must provide centimeter-accurate trajectory estimates. This requirement is satisfied if INS error states are periodically estimated by a Kalman filter that uses GPS carrier phase measurements as filter observables. A pattern of the synthetic phased array that is constructed by adding outputs of individual FFTs (see Figure 6) can be approximated by a sinc function:

where θ is the steering direction, θ* is the direction of the incoming signal, and A is the total length of the array. The sync function corresponds closely to the pattern of the physical phased array for the case in which the distance between individual antennas is equal to a half-wavelength:

Figure 7 illustrates close agreement between patterns of the half-wavelength physical array and a synthetic array using a simulated case where the satellite signal is received from a 45degree angle. In applying equation (17) we can see that the pattern of the synthetic array does not depend on the spatial distance between synthetically generated antenna locations. As a result, this spatial distance can be chosen to provide a desired angular range for the multi-directional beam steering. For our particular purposes, we chose a spatial distance equal to λ/4 so as to cover the angular range between 0 to 180 degrees. In this case, the FFT amplitude that corresponds to the kth frequency harmonic is expressed as follows:

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This spectrum amplitude also serves as a synthetic array output for steering direction θk. As a result, it satisfies the following equation:

Comparison of equations (19) and (20) maps FFT frequencies into beam steering angles:

Equation (22) provides the final expression for the FFTbased multi-directional beam steering for synthetic phased arrays:

values for the antenna steering angles Beam direction Synthetic array defined by FFT frequencies as specified ϕ θ by equation (23). Hence, the 2D Physical array FFT mechanism formulated by equation FIGURE 8 Two-dimensional steering angles (23) simultaneously provides Is and Qs for multiple beam steering angles, which can be applied for multi-directional carrier phase tracking. I and Q values for each FFT frequency grid and its corresponding steering direction are treated independently from other frequency grids. Multi-directional carrier phase tracking is performed by processing I and Q values of each steering direction. Signal parameters for different steering directions can be estimated from I and Q values using an open-loop receiver architecture described in the forthcoming article by F. van Graas et alia (Additional Reources). FFT-based multi-directional tracking will be illustrated later in the section describing simultaneous tracking of direct and multipath signals. So, with the foregoing theoretical background in mind, let’s turn to the feasibility demonstration and experimental verification phases of our discussion.

1D Synthetic Array: Flight Test Results Two-Dimensional Beam Steering

For multi-directional steering in two dimensions, one-dimensional FFTs for the synthetic and physical phased arrays — in accordance with equations (22) and (14) — are combined into a two-dimensional FFT:

In (23), m and n are index numbers of the antenna in the physical and synthetic arrays, respectively, with corresponding steering angles ϕ and θ, as shown in Figure 8.

FFT-Based Multi-Directional Signal Tracking

The outputs of the 2D FFT-based steering procedure that we have described correspond to post-correlation complex amplitudes of incoming signals received for different antenna steering angles. More specifically, the real part of the FFT spectrum represents the in-phase (I) post-correlation values and the imaginary part represents the quadrature (Q) post-correlation www.insidegnss.com

Synthetic generation of 1D antenna arrays was verified using experimental data collected in actual flight environments. Figure 9 shows the configuration of equipment on the Ohio University Avionics Engineering Center (OU AEC) McDonald Douglas DC-3 aircraft used for the flight test. We selected a straight segment of the flight to demonstrate the generation of synthetic arrays, with the aircraft traveling at approximately 63 meters per second. The synthetic array approach was verified using sampled GPS data recorded during the flight test by the AEC’s software instrumentation receiver described in the article by S. Gunawardena et alia (Additional Resources). To implement multi-directional beam steering in the range from 0 to 180 degrees using a single FFT — per Equation (18), antennas in synthetically generated arrays are spatially separated by a quarter-wavelength of the GPS L1 carrier wavelength (approximately five centimeters). As described earlier in this article, quarter-wavelength batches of GPS signal samples are first formed and then processed. The motion trajectory reconstructed by the INS is applied to determine the spatial separation of GPS signal samples in order to combine samples that are quarter-wavelengths apart. The INS motion trajectory is computed from measurements of a low-cost inertial measurement unit (IMU). This unit’s sensor errors are specified as 0.1 degree/second (one sigma) gyro drift and one milligal (one sigma) accelerometer bias. IMU measurements are periodically calibrated in-flight using GPS

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synthetic aperture

nal prior to applying the FFT-based beam steering procedure. Figures 10 and 11 show synthetic array patterns (with 13 and 26 elements, respectively) computed by the FFT-based steering method for the case where the motion of the GPS satellite identified by its pseudorandom noise code — PRN 7 — is wiped off from the incoming signal. An estimated carrier-to-noise ratio (C/N0) for PRN 7 is 47 dB-Hz. In the figures, the synthetic array patterns are represented as normalized signal energy (y-axis) versus steering angle, where the signal energy is normalized such that the maximum energy over the entire steering angular range is equal to one. These figures reveal patterns for cases in which the synthetic aperture corresponds to a 13-element array (Figure 10) and a 26-element array (Figure 11) that use half-wavelength separation between their antennas. In the figures, the maximum energy is observed when the antenna beam is steered towards the satellite. An energy loss is introduced as the beam is steered away from the satellite. Essentially, an energy loss for the angle θ is equivalent to a suppression that would be applied to an interference signal (or any other unwanted signal) from a given angle while the beam is steered towards the satellite. The beamwidth is approximated as the distance between the points for which the energy is degraded by three decibels from its maximum (boresight) value. Hence, the beamwidths are approximately 10 degrees and 5 degrees for the 13-element and 26-element synthetic antenna arrays, respectively.

GPS antenna

OU AEC front-end

Data collection computer (Low-cost IMU mounted inside) FIGURE 9

Flight test setup

carrier phase in order to maintain the centimeter-accurate reconstruction of motion trajectory needed to generate the synthetic phased arrays. For each satellite, the down-conversion frequency f IF, PRN code, and satellite motion are wiped off from the incoming sig-

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Pattern of a one-dimensional synthetic antenna array with 13 elements generated using flight data and FFT-based multi-directional beam steering. PRN 7 satellite motion is wiped off from the incoming signal;

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SV LOS angle

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Array pattern for 26-antenna array

0

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Normalized signal energy, dB

We use ground vehicle test data to demonstrate the generation of 2D synthetic phased arrays. Figure 12 shows the experimental setup in the AEC test van that was used for data collection. Similar to the flight test, we implemented a straight motion trajectory with the van’s velocity at approximately four meters

Array pattern for 13-antenna array

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Pattern of a one-dimensional synthetic antenna array with 26 elements generated using flight data and FFT-based multi-directional beam steering. PRN 7 satellite motion is wiped-off from the incoming signal FIGURE 11

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synthetic aperture

Note t hat t he beam steering capabilities in the crosst rack direct ion were limited by the number of front-end channels (two) currently available in RF front-end GPS antennas the software receiver. This limitation Data collection computer (AGNC IMU mounted inside) can be mitigated by increasing the number of frontFIGURE 12 Ground vehicle test setup end channels and/ or by implementing per second. An AEC two-channel softmulti-platform signal integration techware instrumentation receiver was used niques. to record raw GPS signal samples. IMU Figures 13 and 14 show 2D synthetic data were applied to reconstruct the array patterns generated for the ground motion trajectory for the synthetic array experiment. In these figures, α is the formation. steering angle in the direction of motion Two antennas mounted on the van and β is the steering angle in the crossrooftop formed the array beam in the track direction. Figure 13 shows test direction perpendicular to motion. results for a phased array constructed Array aperture in the direction of using two physical and six synthetic motion was synthesized by observing antennas. these antennas at different spatial locaSimilar to the 1D array case, the tions. maximum signal energy is received We calibrated the system’s interwhen the array beam is steered in the channel and inter-antenna biases in direction of the satellite. As the beam advance of the ground test and removed is being steered away from the sateltheir associated phase delays from raw lite, signal attenuation occurs. At a spesignal samples prior to implementing the cific angular direction, this attenuation synthetic signal processing routines. is equivalent to that which would be Pattern of 2x6 element array

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Pattern of a two-dimensional antenna array that is comprised of two physical and six synthetic antennas. Satellite motion has been wiped off from the incoming signal from PRN4, which had a carrier-tonoise ratio of 49 dB-Hz. www.insidegnss.com

Pattern of 2x31 element array

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SV location FIGURE 13

The following section uses simulated results to demonstrate the feasibility of the FFT-based multi-directional signal tracking with simulated results. For the simulation, a multipath signal was added to the direct satellite signal. Multipath was simulated as a specular reflection from a horizontal planar sur-

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FFT-based Multi-Directional Beam Steering: Simulation Results

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applied to a multipath or an interfering signal coming from this direction. As mentioned previously, beamsteering capabilities in the cross-track direction are currently limited by the number of front-end channels in the receiver. With only two channels available, therefore, the array beam in the cross-track direction is rather wide: approximately 30 degrees. Nevertheless, the experimental results demonstrate the feasibility of generating 2D arrays by using synthetic aperture GPS signal processing and combining signals from multiple antennas. Figure 14 shows the 2D synthetic array pattern for the case where the synthetic aperture is extended to 31 elements. This extension narrows the array beam significantly in the direction of motion. The beamwidth in the crosstrack direction remains unchanged.

Pattern of a two-dimensional antenna array that is comprised of two physical and thirty one synthetic antennas; PRN 4 satellite motion is wiped-off from the incoming signal; PRN 4 C/N0 is 49 dB-Hz FIGURE 14

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synthetic aperture

face collinear to the Y-Z plane. Figure 15 illustrates this multipath scenario. For the FFT-based synthetic array processing, the synthetic aperture corresponds to 20 physical antennas separated by a half-wavelength. A fourelement physical array with half-wavelength antenna separation was simulated to steer the beam in the direction perpendicular to motion. Array beams were steered in multiple directions using 2D FFTs (see Equation [23]). For the direct signal, a C/N0 of 40 dB-Hz was implemented. The multipath power was simulated to be three decibels SV

z multipath

direct path

vrcvr

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Multipath reflection scenario simulated to verify multi-directional beam steering in two dimensions FIGURE 15

Normalized signal energy

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180 120 150 90 90 60 30 0 0 30 60 y axis steering x axis steering angle, deg angle, deg

Simulated FFT-based signal image for a two-dimensional antenna array: Direct and multipath signals are simulated; direct signal carrier-to-noise ratio is 40 dB-Hz; multipath signal power is three decibels lower than the direct signal power; angles between X and Y axes of the antenna array and direct signal are simulated as 90 and 46 degrees, respectively; angles between X and Y axes of the antenna array and multipath signal are simulated as 90 and 134 degrees, respectively; energy peaks are clearly observed for cases where the antenna beam is steered towards the direct signal and multipath FIGURE 16

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below the direct sigDirect phase minus estimated direct phase, m 0.04 nal power. 0.02 Figure 16 shows a 2D signal image 0 constructed using -0.02 the 2D FFT-based -0.04 0 0.2 0.4 0.6 0.8 1 beam steering Time, s method. The plot Multipath phase minus estimated multipath phase, m demonstrates simul0.04 taneous recovery of 0.02 the direct and mul0 tipath signals. F F T - b a s e d -0.02 multi-directional -0.04 0 0.2 0.4 0.6 0.8 1 signal tracking was Time, s implemented and simulated for the FIGURE 17 Simultaneous tracking of direct and multipath signal using FFTcase of simultaneous based multi-directional beam steering tracking of direct and multipath signals for the scenario V = 2 m/s illustrated in Figure 15. FFT-based Is and Qs are applied to track the carrier phase of direct and multipath signals. h = 20 m Y Real and imaginary parts of FFT complex amplitudes for beams steered in the X direction of direct and multipath signals are exploited as I and Q values, respectively. FIGURE 18 Simulation scenario implemented to demonstrate GPS-based SAR imaging Figure 17 illustrates the results of the simulated tracking. Carrier phase tracking errors are shown as differences level. The C/N0 of the reflected signal between true carrier phase (known in was simulated to represent an army tank the simulation) and measured carrier hidden under a dense canopy. phase based on I and Q values provided Analysis of RF GPS data collected by 2D FFT computations. in forestry areas shows that for highStandard deviations of carrier phase elevation satellites the signal is generally errors are evaluated as 3.2 and 4.3 milattenuated by 7 decibels as it propagates limeters for the direct and multipath through the canopy. Therefore, the sigsignals, respectively. Hence, the simulanal attenuation of 14 decibels was introtion results presented demonstrate the duced for the two-way propagation path feasibility of simultaneous tracking of through the canopy, that is, from the satmultiple signals using the FFT-based ellite to the target and from the target to multi-directional beam steering. the receiver. The radar cross section (RCS) of GPS-Based SAR Imaging the target is assumed to be five square Figure 18 illustrates a simulation scenario meters. For the 14-decibel signal attenimplemented to demonstrate GPS-based uation due to the propagation through SAR imaging. the canopy and a five square meter A simulated receiver platform RCS value, the C/N0 of the signal that includes four GPS antennas mounted on is received at the UAV platform is estian unmanned aerial vehicle (UAV) that mated at 17 dB-Hz. is flying at 20 meters above the ground We simulated and processed the C/ with a 2 meters per second ground velocA-code component of the GPS signal. ity. The simulated scenario assumes a To process the GPS signal at a 17 dB-Hz single point reflector located at ground level, a one-second coherent integration m ay/ june 200 9

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Focused SAR image

180 150

Y, m

120 90 60 30 0-10

-5

0 X, m

5

10

Acknowledgment

Target location FIGURE 19

Simulated SAR image for the GPS-based SAR implementation

interval was implemented. Construction of SAR images was based on the 2D FFT-based processing approach discussed in the previous section, augmented by beam focusing techniques discussed in the book by J. C. Curlander and R. N. McDonough (Additional Resources) to avoid image distortions that are due to the motion of the platform. Figure 19 shows an example of a simulated SAR image. To construct this image, steering angles were converted into X and Y Cartesian coordinates using the known height above the ground (20meters). The GPS-based SAR image shown in Figure 19 clearly identifies the presence of a target. Note that the image resolution in the direction of motion is achieved using the synthetic aperture. For the cross-track direction, the image is resolved by focusing the array beam with multiple physical antennas mounted perpendicular to motion. This implementation differs from the classical SAR approach that uses a single antenna and the cross-track image component is resolved using the carrier modulation by a ranging signal. For the GPS case, the chip duration of the C/A-code ranging modulation is 300 meters. Clearly, this resolution is insufficient for most imaging applications. Hence, multipleantenna beam focusing is applied to resolve the cross-track image component. As shown in Figure 19, the multi-antenna focusing approach allows for resolving the cross-track image component within approximately three meters. In other words, the ranging resolution of the C/A code is improved by two orders of magnitude in the simulation scenario.

Conclusions

This article has described the generation of synthetic phased GPS antenna arrays using moving antennas. Signals received from a GPS antenna at different spatial locations are combined into a synthetic phased array to sharpen the array beam withwww.insidegnss.com

out increasing its physical size. We introduced an FFT-based approach to simultaneously steer the array beam in multiple directions and to perform multi-source signal tracking. This approach can be applied for improving GPS robustness to radio-frequency interference, simultaneous tracking of multiple signal sources such as direct signal and multipath reflections, and for recording high-resolution images utilizing GPS signal reflections. Future research in the area of synthetic aperture GPS signal processing will focus on the demonstration of the GPS SAR concept with experimental data and multi-platform signal processing for generating large array apertures in the direction perpendicular to motion. This article is based on a presentation made at the 2009 Institute of Navigation International Technical Meeting in Anaheim, California.

Manufacturers

The low-cost IMU used in the AEC flight test is a Coremicro manufactured by American GNC Corporation, Simi Valley, California, USA.

Authors Andrey Soloviev is a research assistant professor at the University of Florida, Research and Engineering Education Facility. Previously he served as a senior research engineer at the Ohio University Avionics Engineering Center, Athens, Ohio. He holds B.S. and M.S. in Applied Mathematics and Physics from Moscow University of Physics and Technology and a Ph.D. in Electrical Engineering from Ohio University. Soloviev’s research interests focus on all aspects of multi-sensor integration for navigation applications. He is a recipient of the Institute of Navigation (ION) Early Achievement Award and the RTCA’s William Jackson Award. Sanjeev Gunawardena is a senior research engineer and co-principal investigator with the Ohio University Avionics Engineering Center. He earned a Ph.D. in electrical engineering from Ohio University and was the 2007 recipient of the RTCA William E. Jackson award. His research interests include RF systems design, digital systems design, reconfigurable computing, and all aspects of GNSS receivers and signal processing. Frank van Graas is the Fritz J. and Dolores H. Russ Professor of Electrical Engineering and a principal investigator with the Avionics Engineering Center at Ohio University. A Past President of The Institute of Navigation, van Graas received the 1996 Johannes Kepler Award from the ION’s Satellite Division of the ION. His research interests center on all facets of GPS, including aircraft precision approach and landing, attitude determination, and system integration. Mikel Miller is the technical director for the Advanced Guidance Division, Munitions Directorate, Air Force Research Laboratory, Eglin Air Force Base, Florida. He received his Ph.D. in electrical engineering from the Air Force

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synthetic aperture Institute of Technology (AFIT), WPAFB, Ohio. Since 1986, he has focused on navigation system R&D related to GPS, GPS/INS integration, alterative navigation techniques including bio-inspired navigation and signals of opportunity–based navigation, autonomous vehicle navigation and control, and multi-sensor fusion. He is currently responsible for directing both in-house and contracted R&D projects advancing guidance, navigation, and control technology for weapon systems.

Additional Resources [1] Akos, D. M., “A Software Radio Approach to Global Navigation Satellite System Receiver Design,” Ph.D. dissertation, Ohio University, August 1997 [2] Broumandan, A., and T. Lin, A. Moghaddam, D. Lu, J. Nielsen, and G. Lachapelle, “Direction of Arrival Estimation of GNSS Signals Based on Synthetic Antenna Array,” in Proceedings of the ION GNSS-2007, September 2007 [3] Cherniakov, M., and R.Saini, M. Antoniou, R. Zuo, and J. Edwards, “SS-BSAR with Transmitter of Opportunity - Practical Aspects,” in Proceedings of the 3rd EMRS DTC Technical Conference, June 2006 [4] Curlander, J. C., and R. N. McDonough, Synthetic Aperture Radar: Systems and Signal Processing, Hoboken, New Jersey, John Wiley & Sons, 1991 [5] Draganov, S., and L. Haas, “Novel Multipath Mitigation Methods for Ultra-tightly Coupled GNSS/INS Systems,” presented at the “for official use only” (FOUO) session of the ION GNSS-2008, September 2008. [6] Farrell, J. L., “GPS/INS-Streamlined,” NAVIGATION, Journal of the Institute of Navigation, Vol. 49, No. 4, Summer 2002 [7] Gold, K., and R. Silva, R. Worrell, and A. Brown “Space Navigation with Digital Beam Steering GPS Receiver Technology,” in Proceedings of the ION Annual Meeting, June 2003

ment Error Characterization and Compensation,” in Proc. of the ION GNSS-2006, September 2006 [11] Morton, Y. T., and L. L. Liou, D. M. Lin, J. B. Y. Tsui, and Q. Zhou, “Broad Band Interference Cancellation using Digital Beam Forming and a Software GPS Receiver,” in Proceedings of the ION GNSS-2005, September 2005 [12] Nicholson, B. W., and D. M. Upton, S. Cotterill, J. Marchese, T. Upadhyay, and W. E. Vander Velde “Computer Simulation of Digital Beam Forming Adaptive Antennae for GPS Interference Mitigation,” in Proc. of the ION National Technical Meeting, January 1998. [13] Pany, T., and B. Eissfeller, “Demonstration of a Synthetic Phased Array Antenna for Carrier/Code Multipath Mitigation,” in Proc. of the ION GNSS2008, Sep. 2008. [14] Psiaki, M. L., and H. Jung, “Extended Kalman Filter Methods for Tracking Weak GPS Signals,” in Proceedings of the ION GPS-2002, September 2002 [15] Rama Rao, B., and E. N. Rosario, and R. J. Davis, “Eleven Element Beam Steering GPS Antenna Array in a GAS-1 CRPA Footprint,” presented at the FOUO session of the ION GNSS-2008, September 2008 [16] Skolnik, M. I., Introduction to Radar Systems, 3rd ed. New York: McGraw-Hill, 2001 [17] Soloviev, A., and S. Gunawardena, and F. van Graas, “Decoding Navigation Data Messages from Weak GPS Signals,” to appear in IEEE Transactions on Aerospace and Electronic Systems [18] van Graas, F., and A. Soloviev, M. Uijt de Haag, S. Gunawardena, “Comparison of Two Approaches for GNSS Receiver Algorithms: Batch Processing and Sequential Processing Considerations,” to appear in IEEE Journal of Selected Topics in Signal Processing, Special Issue on: Advanced Signal Processing for GNSS and Robust Navigation, August 2009 [16] Zeidan, N. I., and J. L. Garrison, “Bit Synchronization and Doppler Frequency Removal at Very Low Carrier to Noise Ratio Using a Combination of the Viterbi Algorithm with an Extended Kalman Filter,” in Proceedings of the ION GPS/GNSS-2003, September 2003

[8] Gunawardena, S., A. Soloviev, F. van Graas, “Wideband Transform-Domain GPS Instrumentation Receiver for Signal Quality and Anomalous Event Monitoring,” NAVIGATION, Journal of the Institute of Navigation, Vol. 53, No. 4, 2007 [9] Kaplan, E., and C. Hegarty (Editors), Understanding GPS: Principles and Applications, 2nd ed. Norwood, Massachusetts: Artech House, 2006 [10] McGraw, G. A., and C. McDowell, and J. M. Kelly “GPS Anti-Jam Antenna System Measure-

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