Op A 2227
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OPA227 OPA2227 OPA4227
OPA 4
227
OPA
227
OPA 2
227
OPA 42
OPA2
27
OPA228
27
OPA2
227
OPA2228 OPA4228 SBOS110A – MAY 1998 – REVISED JANUARY 2005
High Precision, Low Noise OPERATIONAL AMPLIFIERS FEATURES
DESCRIPTION
● LOW NOISE: 3nV/√Hz ● WIDE BANDWIDTH: OPA227: 8MHz, 2.3V/µs OPA228: 33MHz, 10V/µs
The OPA227 and OPA228 series op amps combine low noise and wide bandwidth with high precision to make them the ideal choice for applications requiring both ac and precision dc performance.
● SETTLING TIME: 5µs (significant improvement over OP-27) ● ● ● ● ● ●
The OPA227 is unity-gain stable and features high slew rate (2.3V/µs) and wide bandwidth (8MHz). The OPA228 is optimized for closed-loop gains of 5 or greater, and offers higher speed with a slew rate of 10V/µs and a bandwidth of 33MHz.
HIGH CMRR: 138dB HIGH OPEN-LOOP GAIN: 160dB LOW INPUT BIAS CURRENT: 10nA max LOW OFFSET VOLTAGE: 75µV max WIDE SUPPLY RANGE: ±2.5V to ±18V OPA227 REPLACES OP-27, LT1007, MAX427
The OPA227 and OPA228 series op amps are ideal for professional audio equipment. In addition, low quiescent current and low cost make them ideal for portable applications requiring high precision.
● OPA228 REPLACES OP-37, LT1037, MAX437
The OPA227 and OPA228 series op amps are pin-for-pin replacements for the industry standard OP-27 and OP-37 with substantial improvements across the board. The dual and quad versions are available for space savings and perchannel cost reduction.
● SINGLE, DUAL, AND QUAD VERSIONS
APPLICATIONS ● ● ● ● ● ● ●
DATA ACQUISITION TELECOM EQUIPMENT GEOPHYSICAL ANALYSIS VIBRATION ANALYSIS SPECTRAL ANALYSIS PROFESSIONAL AUDIO EQUIPMENT ACTIVE FILTERS
The OPA227, OPA228, OPA2227, and OPA2228 are available in DIP-8 and SO-8 packages. The OPA4227 and OPA4228 are available in DIP-14 and SO-14 packages with standard pin configurations. Operation is specified from –40°C to +85°C. OPA4227, OPA4228
● POWER SUPPLY CONTROL SPICE model available for OPA227 at www.ti.com
Out A
1
OPA227, OPA228
Out A
1
Trim
1
8
Trim
–In A
2
–In
2
7
V+
+In A
3
+In
3
6
Output
V–
4
V–
4
5
NC
8 A B
Out D
–In A
2
13
–In D
+In A
3
12
+In D
V+
4
11
V–
+In B
5
10
+In C
A
OPA2227, OPA2228
14 D
V+
7
Out B
6
–In B
5
+In B
B
C
–In B
6
9
–In C
Out B
7
8
Out C
DIP-14, SO-14
DIP-8, SO-8 DIP-8, SO-8 NC = Not Connected
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. Copyright © 1998-2005, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
www.ti.com
SPECIFICATIONS: VS = ±5V to ±15V OPA227 Series At TA = +25°C, and RL = 10kΩ, unless otherwise noted. Boldface limits apply over the specified temperature range, TA = –40°C to +85°C. OPA227PA, UA OPA2227PA, UA OPA4227PA, UA
OPA227P, U OPA2227P, U PARAMETER
CONDITION
OFFSET VOLTAGE Input Offset Voltage VOS OTA = –40°C to +85°Cver Temperature vs Temperature dVOS/dT vs Power Supply PSRR TA = –40°C to +85°C vs Time Channel Separation (dual, quad) INPUT BIAS CURRENT Input Bias Current TA = –40°C to +85°C Input Offset Current TA = –40°C to +85°C
MIN
TYP ±5
±0.1
VS = ±2.5V to ±18V
±0.5
±2.5
IOS
±2.5
Input Voltage Noise Density, f = 10Hz en f = 100Hz f = 1kHz Current Noise Density, f = 1kHz in
90 15 3.5 3 3 0.4
NOISE Input Voltage Noise, f = 0.1Hz to 10Hz
VCM CMRR
INPUT IMPEDANCE Differential Common-Mode AOL
FREQUENCY RESPONSE Gain Bandwidth Product GBW Slew Rate SR Settling Time: 0.1% 0.01% Overload Recovery Time Total Harmonic Distortion + Noise THD+N OUTPUT Voltage Output TA = –40°C to +85°C
VO = (V–)+2V to (V+)–2V, RL = 10kΩ
132 132 132 132
10kΩ 10kΩ 600Ω 600Ω
TEMPERATURE RANGE Specified Range Operating Range Storage Range Thermal Resistance SO-8 Surface Mount DIP-8 DIP-14 SO-14 Surface Mount
±5 ±2.5
VS IQ
✻
IO = 0 IO = 0
±10
✻
±10
✻
±10 ±10
✻ ✻ ✻
✻ ✻ ✻ ✻
160 160
θJA
150 100 80 100
±200
✻ ✻
µV µV µV/°C µV/V µV/V µV/mo µV/V dB
✻ ✻ ✻ ✻
nA nA nA nA
±200 ±2
nVp-p nVrms nV/√Hz nV/√Hz nV/√Hz pA/√Hz ✻
✻
V dB dB
✻ ✻
Ω || pF Ω || pF
✻
dB dB dB dB
✻
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2 (V+)–2 (V+)–3.5 (V+)–3.5
–40 –55 –65
UNITS
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2
±3.7
MAX
✻ ✻ ✻
✻ ✻ ✻ ✻
±45 See Typical Curve
ISC CLOAD
POWER SUPPLY Specified Voltage Range Operating Voltage Range Quiescent Current (per amplifier) TA = –40°C to +85°C
±0.3
±2 ±2
138
(V–)+2 (V–)+2 (V–)+3.5 (V–)+3.5
TYP ±10
8 2.3 5 5.6 1.3 0.00005
G = 1, 10V Step, CL = 100pF G = 1, 10V Step, CL = 100pF VIN • G = VS f = 1kHz, G = 1, VO = 3.5Vrms RL = RL = RL = RL =
±75
±100 ±0.6
107 || 12 109 || 3
VO = (V–)+3.5V to (V+)–3.5V, RL = 600Ω
TA = –40°C to +85°C
TA = –40°C to +85°C Short-Circuit Current Capacitive Load Drive
(V–)+2 120 120
VCM = (V–)+2V to (V+)–2V
VCM = (V–)+2V to (V+)–2V
OPEN-LOOP GAIN Open-Loop Voltage Gain TA = –40°C to +85°C
MIN
0.2 0.2 110
dc f = 1kHz, RL = 5kΩ
IB
INPUT VOLTAGE RANGE Common-Mode Voltage Range Common-Mode Rejection TA = –40°C to +85°C
MAX
MHz V/µs µs µs µs % ✻ ✻ ✻ ✻
V V V V mA
✻ ✻ ✻ ✻
V V mA mA
✻ ✻ ✻
°C °C °C
✻ ✻
±15 ±18 ±3.8 ±4.2
✻ ✻
+85 +125 +150
✻ ✻ ✻
✻
✻ ✻ ✻ ✻
°C/W °C/W °C/W °C/W
✻ Specifications same as OPA227P, U.
2
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
SPECIFICATIONS: VS = ±5V to ±15V OPA228 Series At TA = +25°C, and RL = 10kΩ, unless otherwise noted. Boldface limits apply over the specified temperature range, TA = –40°C to +85°C. OPA228PA, UA OPA2228PA, UA OPA4228PA, UA
OPA228P, U OPA2228P, U PARAMETER
CONDITION
OFFSET VOLTAGE Input Offset Voltage VOS OTA = –40°C to +85°Cver Temperature vs Temperature dVOS/dT vs Power Supply PSRR TA = –40°C to +85°C vs Time Channel Separation (dual, quad) INPUT BIAS CURRENT Input Bias Current TA = –40°C to +85°C Input Offset Current TA = –40°C to +85°C
MIN
TYP ±5
±0.1
VS = ±2.5V to ±18V
±0.5
±2.5
IOS
±2.5
Input Voltage Noise Density, f = 10Hz en f = 100Hz f = 1kHz Current Noise Density, f = 1kHz in
90 15 3.5 3 3 0.4
NOISE Input Voltage Noise, f = 0.1Hz to 10Hz
VCM CMRR
INPUT IMPEDANCE Differential Common-Mode AOL
FREQUENCY RESPONSE Minimum Closed-Loop Gain Gain Bandwidth Product GBW Slew Rate SR Settling Time: 0.1% 0.01% Overload Recovery Time Total Harmonic Distortion + Noise THD+N OUTPUT Voltage Output TA = –40°C to +85°C
VO = (V–)+2V to (V+)–2V, RL = 10kΩ
132 132 132 132
10kΩ 10kΩ 600Ω 600Ω
TEMPERATURE RANGE Specified Range Operating Range Storage Range Thermal Resistance SO-8 Surface Mount DIP-8 DIP-14 SO-14 Surface Mount
±5 ±2.5
VS IQ
✻
IO = 0 IO = 0
±10
✻
±10
✻
±10 ±10
✻ ✻ ✻
✻ ✻ ✻ ✻
160 160
θJA
150 100 80 100
±200
✻ ✻
µV µV µV/°C µV/V µV/V µV/mo µV/V dB
✻ ✻ ✻ ✻
nA nA nA nA
±200 ±2
nVp-p nVrms nV/√Hz nV/√Hz nV/√Hz pA/√Hz ✻
✻
V dB dB
✻ ✻
Ω || pF Ω || pF
✻
dB dB dB dB
✻
✻ ✻ ✻ ✻ ✻ ✻ ✻ (V+)–2 (V+)–2 (V+)–3.5 (V+)–3.5
–40 –55 –65
UNITS
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2
±3.7
MAX
✻ ✻ ✻
✻ ✻ ✻ ✻
±45 See Typical Curve
ISC CLOAD
POWER SUPPLY Specified Voltage Range Operating Voltage Range Quiescent Current (per amplifier) TA = –40°C to +85°C
±0.3
±2 ±2
138
(V–)+2 (V–)+2 (V–)+3.5 (V–)+3.5
TYP ±10
5 33 11 1.5 2 0.6 0.00005
G = 5, 10V Step, CL = 100pF, CF =12pF G = 5, 10V Step, CL = 100pF, CF =12pF VIN • G = VS f = 1kHz, G = 5, VO = 3.5Vrms RL = RL = RL = RL =
±75
±100 ±0.6
107 || 12 109 || 3
VO = (V–)+3.5V to (V+)–3.5V, RL = 600Ω
TA = –40°C to +85°C
TA = –40°C to +85°C Short-Circuit Current Capacitive Load Drive
(V–)+2 120 120
VCM = (V–)+2V to (V+)–2V
VCM = (V–)+2V to (V+)–2V
OPEN-LOOP GAIN Open-Loop Voltage Gain TA = –40°C to +85°C
MIN
0.2 0.2 110
dc f = 1kHz, RL = 5kΩ
IB
INPUT VOLTAGE RANGE Common-Mode Voltage Range Common-Mode Rejection TA = –40°C to +85°C
MAX
V/V MHz V/µs µs µs µs % ✻ ✻ ✻ ✻
V V V V mA
✻ ✻ ✻ ✻
V V mA mA
✻ ✻ ✻
°C °C °C
✻ ✻
±15 ±18 ±3.8 ±4.2
✻ ✻
+85 +125 +150
✻ ✻ ✻
✻
✻ ✻ ✻ ✻
°C/W °C/W °C/W °C/W
✻ Specifications same as OPA228P, U.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
3
ABSOLUTE MAXIMUM RATINGS(1) Supply Voltage .................................................................................. ±18V Signal Input Terminals, Voltage ........................ (V–) –0.7V to (V+) +0.7V Current ....................................................... 20mA Output Short-Circuit(2) .............................................................. Continuous Operating Temperature .................................................. –55°C to +125°C Storage Temperature ..................................................... –65°C to +150°C Junction Temperature ...................................................................... 150°C Lead Temperature (soldering, 10s) ................................................. 300°C NOTE: (1) Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may degrade device reliability. (2) Short-circuit to ground, one amplifier per package.
PACKAGE/ORDERING INFORMATION
ELECTROSTATIC DISCHARGE SENSITIVITY This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
For the most current package and ordering information, see the Package Option Addendum located at the end of this datasheet, or refer to our web site at www.ti.com.
4
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
OPEN-LOOP GAIN/PHASE vs FREQUENCY
OPEN-LOOP GAIN/PHASE vs FREQUENCY
G
AOL (dB)
120 100
φ
80
–20
160
–40
140
–60
120
–80
100
–100
60
–120
0
OPA228
–20 –40
G
–60 –80
φ
80
–100
60
–120 –140
40
–140
40
20
–160
20
–160
0
–180
0
–180
–20 0.01 0.10
1
10
100
1k
–20 0.01 0.10
–200 10k 100k 1M 10M 100M
1
10
100
1k
–200 10k 100k 1M 10M 100M
Frequency (Hz)
Frequency (Hz)
POWER SUPPLY AND COMMON-MODE REJECTION RATIO vs FREQUENCY
INPUT VOLTAGE AND CURRENT NOISE SPECTRAL DENSITY vs FREQUENCY
140
100k
120
Voltage Noise (nV/√Hz) Current Noise (fA/√Hz)
PSRR, CMRR (dB)
+CMRR 100 +PSRR
80 60
–PSRR
40 -20 –0
Current Noise
1k
100
10
Voltage Noise
1 0.1
1
10
100
1k
10k
100k
1M
0.1
1
10
100
1k
10k
Frequency (Hz)
Frequency (Hz)
TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY
TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY
0.01
0.01
OPA227
VOUT = 3.5Vrms
THD+Noise (%)
VOUT = 3.5Vrms
THD+Noise (%)
10k
0.001
0.0001
G = 1, RL = 10kΩ
0.00001
OPA228
0.001
0.0001
G = 1, RL = 10kΩ
0.00001 20
100
1k
10k
20k
20
Frequency (Hz)
1k
10k
50k
Frequency (Hz)
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
100
www.ti.com
5
Phase (°)
140
180
AOL (dB)
OPA227
160
0
Phase (°)
180
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL =10kΩ, and VS = ±15V, unless otherwise noted.
INPUT NOISE VOLTAGE vs TIME
CHANNEL SEPARATION vs FREQUENCY
50nV/div
Channel Separation (dB)
140
120
100
80 Dual and quad devices. G = 1, all channels. Quad measured Channel A to D, or B to C; other combinations yield similiar or improved rejection.
60
40 10
1s/div
100
1k
10k
100k
1M
Frequency (Hz)
VOLTAGE NOISE DISTRIBUTION (10Hz)
OFFSET VOLTAGE PRODUCTION DISTRIBUTION
24
17.5 Typical distribution of packaged units.
Percent of Amplifiers (%)
Percent of Units (%)
15.0
16
8
12.5 10.0 5.5 5.0 2.5
0 0
3.16 3.25 3.34 3.43
3.51 3.60
–150 –135 –120 –105 –90 –75 –60 –45 –30 –15 0 15 30 45 60 75 90 105 120 135 150
0 3.69 3.78
Noise (nV/√Hz)
Offset Voltage (µV)
OFFSET VOLTAGE DRIFT PRODUCTION DISTRIBUTION
WARM-UP OFFSET VOLTAGE DRIFT
12
10 8 Offset Voltage Change (µV)
Percent of Amplifiers (%)
Typical distribution of packaged units.
8
4
6 4 2 0 –2 –4 –6 –8
0
–10 0
0.5
1.0
0
1.5
100
150
200
250
300
Time from Power Supply Turn-On (s)
Offset Voltage Drift (µV)/°C
6
50
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
AOL, CMRR, PSRR vs TEMPERATURE
AOL, CMRR, PSRR vs TEMPERATURE 160
160
AOL
AOL, CMRR, PSRR (dB)
AOL, CMRR, PSRR (dB)
CMRR
140 130 PSRR
120 110 100 90 80
OPA227
70 60 –75
–50
AOL
150
150
CMRR
140 130 PSRR
120 110 100 90 80
OPA228
70 –25
0
25
50
75
100
60 –75
125
–50
–25
0
Short-Circuit Current (mA)
Input Bias Current (nA)
75
100
125
60
1.5 1.0 0.5 0 –0.5 –1.0 –1.5
–40 –20
0
20
40
60
80
50 40 30 20 10 0 –75
100 120 140
–ISC
+ISC
–50
–25
0
25
50
75
100
125
Temperature (°C)
Temperature (°C)
QUIESCENT CURRENT vs SUPPLY VOLTAGE
QUIESCENT CURRENT vs TEMPERATURE 3.8 ±18V ±15V ±12V ±10V
4.5
4.0
±5V ±2.5V
3.5
3.0
Quiescent Current (mA)
5.0
Quiescent Current (mA)
50
SHORT-CIRCUIT CURRENT vs TEMPERATURE
INPUT BIAS CURRENT vs TEMPERATURE 2.0
–2.0 –60
25
Temperature (°C)
Temperature (°C)
3.6
3.4
3.2
3.0
2.8
2.5 –60 –40
–20
0
20
40
60
80
0
100 120 140
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
2
4
6
8
10
12
14
16
18
20
Supply Voltage (±V)
Temperature (°C)
www.ti.com
7
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SLEW RATE vs TEMPERATURE
SLEW RATE vs TEMPERATURE
3.0
12
OPA227
OPA228 10
Positive Slew Rate Negative Slew Rate
Slew Rate (µV/V)
Slew Rate (µV/V)
2.5 2.0 1.5 1.0
8 6 4
RLOAD = 2kΩ CLOAD = 100pF
0.5 0
0 –75
–50
–25
0
25
50
75
100
125
–75
–50
–25
0
75
CHANGE IN INPUT BIAS CURRENT vs POWER SUPPLY VOLTAGE
CHANGE IN INPUT BIAS CURRENT vs COMMON-MODE VOLTAGE
100
125
1.5
1.0
Curve shows normalized change in bias current with respect to VCM = 0V. Typical IB may range from –2nA to +2nA at VCM = 0V.
1.0 0.5 ∆IB (nA)
0.5 0 –0.5
VS = ±15V
0 –0.5
VS = ±5V
–1.0 –1.0
–1.5
–1.5
–2.0 0
5
10
15
20
25
30
35
–15
40
–10
–5
0
5
10
15
Common-Mode Voltage (V)
Supply Voltage (V)
OUTPUT VOLTAGE SWING vs OUTPUT CURRENT
SETTLING TIME vs CLOSED-LOOP GAIN 15
100
VS = ±15V, 10V Step CL = 1500pF RL = 2kΩ
Output Voltage Swing (V)
Settling Time (µs)
50
Temperature (°C)
Curve shows normalized change in bias current with respect to VS = ±10V. Typical IB may range from –2nA to +2nA at VS = ±10V.
1.5
OPA227 0.01%
10
0.1%
OPA228 0.01%
0.1%
1 ±1
±10
±100
V+
14
(V+) –1V
13
(V+) –2V
12
–40°C
125°C 85°C 25°C
11 10 –10
–55°C
85°C
–11
(V+) –3V
–55°C
125°C
–12
(V–) +3V
–40°C 25°C
–13
(V–) +2V
–14
(V–) +1V
–15
V– 0
10
20
30
40
50
60
Output Current (mA)
Gain (V/V)
8
25
Temperature (°C)
2.0
∆IB (nA)
RLOAD = 2kΩ CLOAD = 100pF
2
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SMALL-SIGNAL OVERSHOOT vs LOAD CAPACITANCE
MAXIMUM OUTPUT VOLTAGE vs FREQUENCY 30
70
VS = ±15V
OPA227
OPA227 60
Gain = +10
50
20
Overshoot (%)
Output Voltage (Vp-p)
25
15 VS = ±5V
10
40 30 20
5 0
Gain = –10
Gain = –1 Gain = +1
10 0
1k
10k
100k
1M
10M
1
10
100
1k
10k
Frequency (Hz)
Load Capacitance (pF)
LARGE-SIGNAL STEP RESPONSE G = –1, CL = 1500pF
SMALL-SIGNAL STEP RESPONSE G = +1, CL = 1000pF
OPA227
100k
2V/div
25mV/div
OPA227
400ns/div
5µs/div
SMALL-SIGNAL STEP RESPONSE G = +1, CL = 5pF
25mV/div
OPA227
400ns/div
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
9
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SMALL-SIGNAL OVERSHOOT vs LOAD CAPACITANCE
MAXIMUM OUTPUT VOLTAGE vs FREQUENCY 30
70
VS = ±15V
OPA228
OPA228 60 50
20
Overshoot (%)
Output Voltage (Vp-p)
25
15 VS = ±5V
10
G = –100 40 30 G = +100 20 G = ±10
5
10 0
0 1k
10k
100k
1M
1
10M
10
Frequency (Hz)
100
1k
10k
100k
Load Capacitance (pF)
SMALL-SIGNAL STEP RESPONSE G = +10, CL = 1000pF, RL = 1.8kΩ
LARGE-SIGNAL STEP RESPONSE G = –10, CL = 100pF
OPA228
5V/div
200mV/div
OPA228
500ns/div
2µs/div
SMALL-SIGNAL STEP RESPONSE G = +10, CL = 5pF, RL = 1.8kΩ
200mV/div
OPA228
500ns/div
10
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
APPLICATIONS INFORMATION
Trim range exceeds offset voltage specification
V+
The OPA227 and OPA228 series are precision op amps with very low noise. The OPA227 series is unity-gain stable with a slew rate of 2.3V/µs and 8MHz bandwidth. The OPA228 series is optimized for higher-speed applications with gains of 5 or greater, featuring a slew rate of 10V/µs and 33MHz bandwidth. Applications with noisy or high impedance power supplies may require decoupling capacitors close to the device pins. In most cases, 0.1µF capacitors are adequate.
0.1µF 20kΩ 7
2
1 8
OPA227 6
3
OPA227 and OPA228 single op amps only. Use offset adjust pins only to null offset voltage of op amp. See text.
4
0.1µF V–
OFFSET VOLTAGE AND DRIFT The OPA227 and OPA228 series have very low offset voltage and drift. To achieve highest dc precision, circuit layout and mechanical conditions should be optimized. Connections of dissimilar metals can generate thermal potentials at the op amp inputs which can degrade the offset voltage and drift. These thermocouple effects can exceed the inherent drift of the amplifier and ultimately degrade its performance. The thermal potentials can be made to cancel by assuring that they are equal at both input terminals. In addition: • Keep thermal mass of the connections made to the two input terminals similar. • Locate heat sources as far as possible from the critical input circuitry. • Shield op amp and input circuitry from air currents such as those created by cooling fans.
FIGURE 1. OPA227 Offset Voltage Trim Circuit. amp. This adjustment should not be used to compensate for offsets created elsewhere in the system since this can introduce additional temperature drift. INPUT PROTECTION Back-to-back diodes (see Figure 2) are used for input protection on the OPA227 and OPA228. Exceeding the turn-on threshold of these diodes, as in a pulse condition, can cause current to flow through the input protection diodes due to the amplifier’s finite slew rate. Without external current-limiting resistors, the input devices can be destroyed. Sources of high input current can cause subtle damage to the amplifier. Although the unit may still be functional, important parameters such as input offset voltage, drift, and noise may shift.
OPERATING VOLTAGE OPA227 and OPA228 series op amps operate from ±2.5V to ±18V supplies with excellent performance. Unlike most op amps which are specified at only one supply voltage, the OPA227 series is specified for real-world applications; a single set of specifications applies over the ±5V to ±15V supply range. Specifications are assured for applications between ±5V and ±15V power supplies. Some applications do not require equal positive and negative output voltage swing. Power supply voltages do not need to be equal. The OPA227 and OPA228 series can operate with as little as 5V between the supplies and with up to 36V between the supplies. For example, the positive supply could be set to 25V with the negative supply at –5V or vice-versa. In addition, key parameters are assured over the specified temperature range, –40°C to +85°C. Parameters which vary significantly with operating voltage or temperature are shown in the Typical Performance Curves. OFFSET VOLTAGE ADJUSTMENT The OPA227 and OPA228 series are laser-trimmed for very low offset and drift so most applications will not require external adjustment. However, the OPA227 and OPA228 (single versions) provide offset voltage trim connections on pins 1 and 8. Offset voltage can be adjusted by connecting a potentiometer as shown in Figure 1. This adjustment should be used only to null the offset of the op
RF 500Ω
–
OPA227 Input
+
FIGURE 2. Pulsed Operation. When using the OPA227 as a unity-gain buffer (follower), the input current should be limited to 20mA. This can be accomplished by inserting a feedback resistor or a resistor in series with the source. Sufficient resistor size can be calculated: RX = VS/20mA – RSOURCE where RX is either in series with the source or inserted in the feedback path. For example, for a 10V pulse (VS = 10V), total loop resistance must be 500Ω. If the source impedance is large enough to sufficiently limit the current on its own, no additional resistors are needed. The size of any external resistors must be carefully chosen since they will increase noise. See the Noise Performance section of this data sheet for further information on noise calculation. Figure 2 shows an example implementing a currentlimiting feedback resistor.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
Output
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11
INPUT BIAS CURRENT CANCELLATION
NOISE PERFORMANCE
The input bias current of the OPA227 and OPA228 series is internally compensated with an equal and opposite cancellation current. The resulting input bias current is the difference between with input bias current and the cancellation current. The residual input bias current can be positive or negative.
Figure 4 shows total circuit noise for varying source impedances with the op amp in a unity-gain configuration (no feedback resistor network, therefore no additional noise contributions). Two different op amps are shown with total circuit noise calculated. The OPA227 has very low voltage noise, making it ideal for low source impedances (less than 20kΩ). A similar precision op amp, the OPA277, has somewhat higher voltage noise but lower current noise. It provides excellent noise performance at moderate source impedance (10kΩ to 100kΩ). Above 100kΩ, a FET-input op amp such as the OPA132 (very low current noise) may provide improved performance. The equation is shown for the calculation of the total circuit noise. Note that en = voltage noise, in = current noise, RS = source impedance, k = Boltzmann’s constant = 1.38 • 10–23 J/K and T is temperature in K. For more details on calculating noise, see the insert titled “Basic Noise Calculations.”
When the bias current is cancelled in this manner, the input bias current and input offset current are approximately equal. A resistor added to cancel the effect of the input bias current (as shown in Figure 3) may actually increase offset and noise and is therefore not recommended. Conventional Op Amp Configuration R2 R1
Not recommended for OPA227
RB = R2 || R1
Op Amp
VOLTAGE NOISE SPECTRAL DENSITY vs SOURCE RESISTANCE
External Cancellation Resistor Votlage Noise Spectral Density, E0 Typical at 1k (V/√Hz)
1.00+03
Recommended OPA227 Configuration R2 R1
OPA227
EO
OPA227
RS
1.00E+02
OPA277
OPA277
Resistor Noise
OPA227
1.00E+01
Resistor Noise EO2 = en2 + (in RS)2 + 4kTRS 1.00E+00
No cancellation resistor. See text.
100
1k
10k
100k
10M
Source Resistance, RS (Ω)
FIGURE 4. Noise Performance of the OPA227 in UnityGain Buffer Configuration.
FIGURE 3. Input Bias Current Cancellation.
BASIC NOISE CALCULATIONS Design of low noise op amp circuits requires careful consideration of a variety of possible noise contributors: noise from the signal source, noise generated in the op amp, and noise from the feedback network resistors. The total noise of the circuit is the root-sum-square combination of all noise components. The resistive portion of the source impedance produces thermal noise proportional to the square root of the resistance. This function is shown plotted in Figure 4. Since the source impedance is usually fixed, select the op amp and the feedback resistors to minimize their contribution to the total noise. Figure 4 shows total noise for varying source impedances with the op amp in a unity-gain configuration (no feedback resistor network and therefore no additional noise contributions). The operational amplifier itself contributes both a voltage noise component and a current
12
noise component. The voltage noise is commonly modeled as a time-varying component of the offset voltage. The current noise is modeled as the time-varying component of the input bias current and reacts with the source resistance to create a voltage component of noise. Consequently, the lowest noise op amp for a given application depends on the source impedance. For low source impedance, current noise is negligible and voltage noise generally dominates. For high source impedance, current noise may dominate. Figure 5 shows both inverting and noninverting op amp circuit configurations with gain. In circuit configurations with gain, the feedback network resistors also contribute noise. The current noise of the op amp reacts with the feedback resistors to create additional noise components. The feedback resistor values can generally be chosen to make these noise sources negligible. The equations for total noise are shown for both configurations. OPA227, 2227, 4227 OPA228, 2228, 4228
www.ti.com
SBOS110A
Noise in Noninverting Gain Configuration R2
Noise at the output: 2
R R 2 2 E O 2 = 1 + 2 e n 2 + e12 + e 2 2 + (i n R 2 ) + e S 2 + (i n R S ) 1 + 2 R1 R1
R1 EO
RS
VS
2
R Where eS = √4kTRS • 1 + 2 = thermal noise of RS R1 R e1 = √4kTR1 • 2 R1
= thermal noise of R1
e2 = √4kTR2
= thermal noise of R2
Noise in Inverting Gain Configuration R2
Noise at the output: 2
R1
RS
EO
VS
R2 2 2 2 2 2 E O 2 = 1 + e n + e1 + e 2 + (i n R 2 ) + e S R1 + R S
R2 Where eS = √4kTRS • = thermal noise of RS R1 + R S R2 e1 = √4kTR1 • = thermal noise of R1 R1 + R S
e2 = √4kTR2
= thermal noise of R2
For the OPA227 and OPA228 series op amps at 1kHz, en = 3nV/√Hz and in = 0.4pA/√Hz.
FIGURE 5. Noise Calculation in Gain Configurations.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
13
R1 2MΩ
R2 2MΩ
R8 402kΩ
R11 178kΩ
R3 1kΩ
R4 9.09kΩ
C4 22nF
C6 10nF
R6 40.2kΩ C2 1µF
C1 1µF
U1
C3 0.47µF
(OPA227) Input from Device Under Test
R7 97.6kΩ
R9 178kΩ
2 3
U2
R10 226kΩ
2
6
(OPA227)
C5 0.47µF
3
U3
6
VOUT
(OPA227)
R5 634kΩ
FIGURE 6. 0.1Hz to 10Hz Bandpass Filter Used to Test Wideband Noise of the OPA227 and OPA228 Series. USING THE OPA228 IN LOW GAINS The OPA228 family is intended for applications with signal gains of 5 or greater, but it is possible to take advantage of their high speed in lower gains. Without external compensation, the OPA228 has sufficient phase margin to maintain stability in unity gain with purely resistive loads. However, the addition of load capacitance can reduce the phase margin and destabilize the op amp.
22pF
100kΩ 10Ω
2 3
OPA227
6
VOUT
Device Under Test
FIGURE 7. Noise Test Circuit. Figure 6 shows the 0.1Hz 10Hz bandpass filter used to test the noise of the OPA227 and OPA228. The filter circuit was designed using Texas Instruments’ FilterPro software (available at www.ti.com). Figure 7 shows the configuration of the OPA227 and OPA228 for noise testing.
14
A variety of compensation techniques have been evaluated specifically for use with the OPA228. The recommended configuration consists of an additional capacitor (CF) in parallel with the feedback resistance, as shown in Figures 8 and 11. This feedback capacitor serves two purposes in compensating the circuit. The op amp’s input capacitance and the feedback resistors interact to cause phase shift that can result in instability. CF compensates the input capacitance, minimizing peaking. Additionally, at high frequencies, the closed-loop gain of the amplifier is strongly influenced by the ratio of the input capacitance and the feedback capacitor. Thus, CF can be selected to yield good stability while maintaining high speed.
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
Without external compensation, the noise specification of the OPA228 is the same as that for the OPA227 in gains of 5 or greater. With the additional external compensation, the output noise of the of the OPA228 will be higher. The amount of noise increase is directly related to the increase in high frequency closed-loop gain established by the CIN/ CF ratio. Figures 8 and 11 show the recommended circuit for gains of +2 and –2, respectively. The figures suggest approximate
values for CF. Because compensation is highly dependent on circuit design, board layout, and load conditions, CF should be optimized experimentally for best results. Figures 9 and 10 show the large- and small-signal step responses for the G = +2 configuration with 100pF load capacitance. Figures 12 and 13 show the large- and smallsignal step responses for the G = –2 configuration with 100pF load capacitance.
15pF
22pF
1kΩ
2kΩ
2kΩ
2kΩ
OPA228
OPA228 2kΩ
2kΩ
100pF
FIGURE 11. Compensation for OPA228 for G = –2.
5mV/div
5mV/div
FIGURE 8. Compensation of the OPA228 for G =+2.
OPA228
OPA228
400ns/div
400ns/div
FIGURE 12. Large-Signal Step Response, G = –2, CLOAD = 100pF, Input Signal = 5Vp-p.
25mV/div
25mV/div
FIGURE 9. Large-Signal Step Response, G = +2, CLOAD = 100pF, Input Signal = 5Vp-p.
OPA228
OPA228
200ns/div
200ns/div
FIGURE 10. Small-Signal Step Response, G = +2, CLOAD = 100pF, Input Signal = 50mVp-p.
FIGURE 13. Small-Signal Step Response, G = –2, CLOAD = 100pF, Input Signal = 50mVp-p.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
100pF
www.ti.com
15
1.1kΩ 1.43kΩ
2.2nF
dc Gain = 1
330pF 1.1kΩ
1.65kΩ
VIN
1.43kΩ
1.91kΩ
OPA227
33nF
2.21kΩ
OPA227
68nF
VOUT 10nF
fN = 13.86kHz
fN = 20.33kHz
Q = 1.186
Q = 4.519
f = 7.2kHz
FIGURE 14. Three-Pole, 20kHz Low Pass, 0.5dB Chebyshev Filter.
20pF 0.1µF
100Ω
TTL INPUT
GAIN
“1” “0”
+1 –1
100kΩ
9.76kΩ
500Ω
2 3
OPA227
6
Output
10kΩ
Input D1
Dexter 1M Thermopile Detector
NOTE: Use metal film resistors and plastic film capacitor. Circuit must be well shielded to achieve low noise.
D2
TTL In
FIGURE 15. Long-Wavelength Infrared Detector Amplifier.
16
2 4.99kΩ S1 S2
3
6
OPA227
Output
8 1 4.75kΩ
Responsivity ≈ 2.5 x 104V/W Output Noise ≈ 30µVrms, 0.1Hz to 10Hz
Balance Trim
4.75kΩ
1kΩ
DG188 Offset Trim
+VCC
FIGURE 16. High Performance Synchronous Demodulator.
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
+15V
0.1µF 1kΩ
1kΩ Audio In
1/2 OPA2227 200Ω To Headphone
200Ω
1/2 OPA2227 This application uses two op amps in parallel for higher output current drive.
0.1µF
–15V
FIGURE 17. Headphone Amplifier.
Bass Tone Control R1 7.5kΩ
R2 50kΩ 3
1
CW
2
R3 7.5kΩ
R10 100kΩ
Midrange Tone Control C1 940pF
R4 2.7kΩ VIN
R5 50kΩ 3
CW
1 2
R6 2.7kΩ C2 0.0047µF
Treble Tone Control R7 7.5kΩ
R8 50kΩ 3
CW
1 2
R9 7.5kΩ
C3 680pF
R11 100kΩ
2 3
OPA227
6
VOUT
FIGURE 18. Three-Band ActiveTone Control (bass, midrange and treble). OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
17
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
PACKAGING INFORMATION Orderable Device
Status (1)
Package Type
Package Drawing
Pins Package Eco Plan (2) Qty
OPA2227P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227U
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5E4
ACTIVE
SOIC
D
8
2500
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5G4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA/2K5E4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UAE4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UE4
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2228P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228U
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228U/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228UA
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
Addendum-Page 1
Pb-Free (RoHS)
Lead/Ball Finish
MSL Peak Temp (3)
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
Orderable Device
Status (1)
Package Type
Package Drawing
Pins Package Eco Plan (2) Qty
OPA227PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227U
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227U/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA/2K5
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA/2K5G4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228U
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA228UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227PA
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4227PAG4
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4227UA
ACTIVE
SOIC
D
14
58
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UA/2K5
ACTIVE
SOIC
D
14
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UA/2K5G4
ACTIVE
SOIC
D
14
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UAG4
ACTIVE
SOIC
D
14
58
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4228PA
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4228UA
ACTIVE
SOIC
D
14
58
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA4228UA/2K5
ACTIVE
SOIC
D
14
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
Addendum-Page 2
Lead/Ball Finish
MSL Peak Temp (3)
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
(1)
The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 3
MECHANICAL DATA MPDI001A – JANUARY 1995 – REVISED JUNE 1999
P (R-PDIP-T8)
PLASTIC DUAL-IN-LINE
0.400 (10,60) 0.355 (9,02) 8
5
0.260 (6,60) 0.240 (6,10)
1
4 0.070 (1,78) MAX 0.325 (8,26) 0.300 (7,62)
0.020 (0,51) MIN
0.015 (0,38) Gage Plane
0.200 (5,08) MAX Seating Plane
0.010 (0,25) NOM
0.125 (3,18) MIN
0.100 (2,54) 0.021 (0,53) 0.015 (0,38)
0.430 (10,92) MAX
0.010 (0,25) M
4040082/D 05/98 NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. Falls within JEDEC MS-001
For the latest package information, go to http://www.ti.com/sc/docs/package/pkg_info.htm
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• DALLAS, TEXAS 75265
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OPA 4
227
OPA
227
OPA 2
227
OPA 42
OPA2
27
OPA228
27
OPA2
227
OPA2228 OPA4228 SBOS110A – MAY 1998 – REVISED JANUARY 2005
High Precision, Low Noise OPERATIONAL AMPLIFIERS FEATURES
DESCRIPTION
● LOW NOISE: 3nV/√Hz ● WIDE BANDWIDTH: OPA227: 8MHz, 2.3V/µs OPA228: 33MHz, 10V/µs
The OPA227 and OPA228 series op amps combine low noise and wide bandwidth with high precision to make them the ideal choice for applications requiring both ac and precision dc performance.
● SETTLING TIME: 5µs (significant improvement over OP-27) ● ● ● ● ● ●
The OPA227 is unity-gain stable and features high slew rate (2.3V/µs) and wide bandwidth (8MHz). The OPA228 is optimized for closed-loop gains of 5 or greater, and offers higher speed with a slew rate of 10V/µs and a bandwidth of 33MHz.
HIGH CMRR: 138dB HIGH OPEN-LOOP GAIN: 160dB LOW INPUT BIAS CURRENT: 10nA max LOW OFFSET VOLTAGE: 75µV max WIDE SUPPLY RANGE: ±2.5V to ±18V OPA227 REPLACES OP-27, LT1007, MAX427
The OPA227 and OPA228 series op amps are ideal for professional audio equipment. In addition, low quiescent current and low cost make them ideal for portable applications requiring high precision.
● OPA228 REPLACES OP-37, LT1037, MAX437
The OPA227 and OPA228 series op amps are pin-for-pin replacements for the industry standard OP-27 and OP-37 with substantial improvements across the board. The dual and quad versions are available for space savings and perchannel cost reduction.
● SINGLE, DUAL, AND QUAD VERSIONS
APPLICATIONS ● ● ● ● ● ● ●
DATA ACQUISITION TELECOM EQUIPMENT GEOPHYSICAL ANALYSIS VIBRATION ANALYSIS SPECTRAL ANALYSIS PROFESSIONAL AUDIO EQUIPMENT ACTIVE FILTERS
The OPA227, OPA228, OPA2227, and OPA2228 are available in DIP-8 and SO-8 packages. The OPA4227 and OPA4228 are available in DIP-14 and SO-14 packages with standard pin configurations. Operation is specified from –40°C to +85°C. OPA4227, OPA4228
● POWER SUPPLY CONTROL SPICE model available for OPA227 at www.ti.com
Out A
1
OPA227, OPA228
Out A
1
Trim
1
8
Trim
–In A
2
–In
2
7
V+
+In A
3
+In
3
6
Output
V–
4
V–
4
5
NC
8 A B
Out D
–In A
2
13
–In D
+In A
3
12
+In D
V+
4
11
V–
+In B
5
10
+In C
A
OPA2227, OPA2228
14 D
V+
7
Out B
6
–In B
5
+In B
B
C
–In B
6
9
–In C
Out B
7
8
Out C
DIP-14, SO-14
DIP-8, SO-8 DIP-8, SO-8 NC = Not Connected
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. Copyright © 1998-2005, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
www.ti.com
SPECIFICATIONS: VS = ±5V to ±15V OPA227 Series At TA = +25°C, and RL = 10kΩ, unless otherwise noted. Boldface limits apply over the specified temperature range, TA = –40°C to +85°C. OPA227PA, UA OPA2227PA, UA OPA4227PA, UA
OPA227P, U OPA2227P, U PARAMETER
CONDITION
OFFSET VOLTAGE Input Offset Voltage VOS OTA = –40°C to +85°Cver Temperature vs Temperature dVOS/dT vs Power Supply PSRR TA = –40°C to +85°C vs Time Channel Separation (dual, quad) INPUT BIAS CURRENT Input Bias Current TA = –40°C to +85°C Input Offset Current TA = –40°C to +85°C
MIN
TYP ±5
±0.1
VS = ±2.5V to ±18V
±0.5
±2.5
IOS
±2.5
Input Voltage Noise Density, f = 10Hz en f = 100Hz f = 1kHz Current Noise Density, f = 1kHz in
90 15 3.5 3 3 0.4
NOISE Input Voltage Noise, f = 0.1Hz to 10Hz
VCM CMRR
INPUT IMPEDANCE Differential Common-Mode AOL
FREQUENCY RESPONSE Gain Bandwidth Product GBW Slew Rate SR Settling Time: 0.1% 0.01% Overload Recovery Time Total Harmonic Distortion + Noise THD+N OUTPUT Voltage Output TA = –40°C to +85°C
VO = (V–)+2V to (V+)–2V, RL = 10kΩ
132 132 132 132
10kΩ 10kΩ 600Ω 600Ω
TEMPERATURE RANGE Specified Range Operating Range Storage Range Thermal Resistance SO-8 Surface Mount DIP-8 DIP-14 SO-14 Surface Mount
±5 ±2.5
VS IQ
✻
IO = 0 IO = 0
±10
✻
±10
✻
±10 ±10
✻ ✻ ✻
✻ ✻ ✻ ✻
160 160
θJA
150 100 80 100
±200
✻ ✻
µV µV µV/°C µV/V µV/V µV/mo µV/V dB
✻ ✻ ✻ ✻
nA nA nA nA
±200 ±2
nVp-p nVrms nV/√Hz nV/√Hz nV/√Hz pA/√Hz ✻
✻
V dB dB
✻ ✻
Ω || pF Ω || pF
✻
dB dB dB dB
✻
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2 (V+)–2 (V+)–3.5 (V+)–3.5
–40 –55 –65
UNITS
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2
±3.7
MAX
✻ ✻ ✻
✻ ✻ ✻ ✻
±45 See Typical Curve
ISC CLOAD
POWER SUPPLY Specified Voltage Range Operating Voltage Range Quiescent Current (per amplifier) TA = –40°C to +85°C
±0.3
±2 ±2
138
(V–)+2 (V–)+2 (V–)+3.5 (V–)+3.5
TYP ±10
8 2.3 5 5.6 1.3 0.00005
G = 1, 10V Step, CL = 100pF G = 1, 10V Step, CL = 100pF VIN • G = VS f = 1kHz, G = 1, VO = 3.5Vrms RL = RL = RL = RL =
±75
±100 ±0.6
107 || 12 109 || 3
VO = (V–)+3.5V to (V+)–3.5V, RL = 600Ω
TA = –40°C to +85°C
TA = –40°C to +85°C Short-Circuit Current Capacitive Load Drive
(V–)+2 120 120
VCM = (V–)+2V to (V+)–2V
VCM = (V–)+2V to (V+)–2V
OPEN-LOOP GAIN Open-Loop Voltage Gain TA = –40°C to +85°C
MIN
0.2 0.2 110
dc f = 1kHz, RL = 5kΩ
IB
INPUT VOLTAGE RANGE Common-Mode Voltage Range Common-Mode Rejection TA = –40°C to +85°C
MAX
MHz V/µs µs µs µs % ✻ ✻ ✻ ✻
V V V V mA
✻ ✻ ✻ ✻
V V mA mA
✻ ✻ ✻
°C °C °C
✻ ✻
±15 ±18 ±3.8 ±4.2
✻ ✻
+85 +125 +150
✻ ✻ ✻
✻
✻ ✻ ✻ ✻
°C/W °C/W °C/W °C/W
✻ Specifications same as OPA227P, U.
2
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
SPECIFICATIONS: VS = ±5V to ±15V OPA228 Series At TA = +25°C, and RL = 10kΩ, unless otherwise noted. Boldface limits apply over the specified temperature range, TA = –40°C to +85°C. OPA228PA, UA OPA2228PA, UA OPA4228PA, UA
OPA228P, U OPA2228P, U PARAMETER
CONDITION
OFFSET VOLTAGE Input Offset Voltage VOS OTA = –40°C to +85°Cver Temperature vs Temperature dVOS/dT vs Power Supply PSRR TA = –40°C to +85°C vs Time Channel Separation (dual, quad) INPUT BIAS CURRENT Input Bias Current TA = –40°C to +85°C Input Offset Current TA = –40°C to +85°C
MIN
TYP ±5
±0.1
VS = ±2.5V to ±18V
±0.5
±2.5
IOS
±2.5
Input Voltage Noise Density, f = 10Hz en f = 100Hz f = 1kHz Current Noise Density, f = 1kHz in
90 15 3.5 3 3 0.4
NOISE Input Voltage Noise, f = 0.1Hz to 10Hz
VCM CMRR
INPUT IMPEDANCE Differential Common-Mode AOL
FREQUENCY RESPONSE Minimum Closed-Loop Gain Gain Bandwidth Product GBW Slew Rate SR Settling Time: 0.1% 0.01% Overload Recovery Time Total Harmonic Distortion + Noise THD+N OUTPUT Voltage Output TA = –40°C to +85°C
VO = (V–)+2V to (V+)–2V, RL = 10kΩ
132 132 132 132
10kΩ 10kΩ 600Ω 600Ω
TEMPERATURE RANGE Specified Range Operating Range Storage Range Thermal Resistance SO-8 Surface Mount DIP-8 DIP-14 SO-14 Surface Mount
±5 ±2.5
VS IQ
✻
IO = 0 IO = 0
±10
✻
±10
✻
±10 ±10
✻ ✻ ✻
✻ ✻ ✻ ✻
160 160
θJA
150 100 80 100
±200
✻ ✻
µV µV µV/°C µV/V µV/V µV/mo µV/V dB
✻ ✻ ✻ ✻
nA nA nA nA
±200 ±2
nVp-p nVrms nV/√Hz nV/√Hz nV/√Hz pA/√Hz ✻
✻
V dB dB
✻ ✻
Ω || pF Ω || pF
✻
dB dB dB dB
✻
✻ ✻ ✻ ✻ ✻ ✻ ✻ (V+)–2 (V+)–2 (V+)–3.5 (V+)–3.5
–40 –55 –65
UNITS
✻ ✻ ✻ ✻ ✻ ✻ (V+)–2
±3.7
MAX
✻ ✻ ✻
✻ ✻ ✻ ✻
±45 See Typical Curve
ISC CLOAD
POWER SUPPLY Specified Voltage Range Operating Voltage Range Quiescent Current (per amplifier) TA = –40°C to +85°C
±0.3
±2 ±2
138
(V–)+2 (V–)+2 (V–)+3.5 (V–)+3.5
TYP ±10
5 33 11 1.5 2 0.6 0.00005
G = 5, 10V Step, CL = 100pF, CF =12pF G = 5, 10V Step, CL = 100pF, CF =12pF VIN • G = VS f = 1kHz, G = 5, VO = 3.5Vrms RL = RL = RL = RL =
±75
±100 ±0.6
107 || 12 109 || 3
VO = (V–)+3.5V to (V+)–3.5V, RL = 600Ω
TA = –40°C to +85°C
TA = –40°C to +85°C Short-Circuit Current Capacitive Load Drive
(V–)+2 120 120
VCM = (V–)+2V to (V+)–2V
VCM = (V–)+2V to (V+)–2V
OPEN-LOOP GAIN Open-Loop Voltage Gain TA = –40°C to +85°C
MIN
0.2 0.2 110
dc f = 1kHz, RL = 5kΩ
IB
INPUT VOLTAGE RANGE Common-Mode Voltage Range Common-Mode Rejection TA = –40°C to +85°C
MAX
V/V MHz V/µs µs µs µs % ✻ ✻ ✻ ✻
V V V V mA
✻ ✻ ✻ ✻
V V mA mA
✻ ✻ ✻
°C °C °C
✻ ✻
±15 ±18 ±3.8 ±4.2
✻ ✻
+85 +125 +150
✻ ✻ ✻
✻
✻ ✻ ✻ ✻
°C/W °C/W °C/W °C/W
✻ Specifications same as OPA228P, U.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
3
ABSOLUTE MAXIMUM RATINGS(1) Supply Voltage .................................................................................. ±18V Signal Input Terminals, Voltage ........................ (V–) –0.7V to (V+) +0.7V Current ....................................................... 20mA Output Short-Circuit(2) .............................................................. Continuous Operating Temperature .................................................. –55°C to +125°C Storage Temperature ..................................................... –65°C to +150°C Junction Temperature ...................................................................... 150°C Lead Temperature (soldering, 10s) ................................................. 300°C NOTE: (1) Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may degrade device reliability. (2) Short-circuit to ground, one amplifier per package.
PACKAGE/ORDERING INFORMATION
ELECTROSTATIC DISCHARGE SENSITIVITY This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
For the most current package and ordering information, see the Package Option Addendum located at the end of this datasheet, or refer to our web site at www.ti.com.
4
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
OPEN-LOOP GAIN/PHASE vs FREQUENCY
OPEN-LOOP GAIN/PHASE vs FREQUENCY
G
AOL (dB)
120 100
φ
80
–20
160
–40
140
–60
120
–80
100
–100
60
–120
0
OPA228
–20 –40
G
–60 –80
φ
80
–100
60
–120 –140
40
–140
40
20
–160
20
–160
0
–180
0
–180
–20 0.01 0.10
1
10
100
1k
–20 0.01 0.10
–200 10k 100k 1M 10M 100M
1
10
100
1k
–200 10k 100k 1M 10M 100M
Frequency (Hz)
Frequency (Hz)
POWER SUPPLY AND COMMON-MODE REJECTION RATIO vs FREQUENCY
INPUT VOLTAGE AND CURRENT NOISE SPECTRAL DENSITY vs FREQUENCY
140
100k
120
Voltage Noise (nV/√Hz) Current Noise (fA/√Hz)
PSRR, CMRR (dB)
+CMRR 100 +PSRR
80 60
–PSRR
40 -20 –0
Current Noise
1k
100
10
Voltage Noise
1 0.1
1
10
100
1k
10k
100k
1M
0.1
1
10
100
1k
10k
Frequency (Hz)
Frequency (Hz)
TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY
TOTAL HARMONIC DISTORTION + NOISE vs FREQUENCY
0.01
0.01
OPA227
VOUT = 3.5Vrms
THD+Noise (%)
VOUT = 3.5Vrms
THD+Noise (%)
10k
0.001
0.0001
G = 1, RL = 10kΩ
0.00001
OPA228
0.001
0.0001
G = 1, RL = 10kΩ
0.00001 20
100
1k
10k
20k
20
Frequency (Hz)
1k
10k
50k
Frequency (Hz)
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
100
www.ti.com
5
Phase (°)
140
180
AOL (dB)
OPA227
160
0
Phase (°)
180
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL =10kΩ, and VS = ±15V, unless otherwise noted.
INPUT NOISE VOLTAGE vs TIME
CHANNEL SEPARATION vs FREQUENCY
50nV/div
Channel Separation (dB)
140
120
100
80 Dual and quad devices. G = 1, all channels. Quad measured Channel A to D, or B to C; other combinations yield similiar or improved rejection.
60
40 10
1s/div
100
1k
10k
100k
1M
Frequency (Hz)
VOLTAGE NOISE DISTRIBUTION (10Hz)
OFFSET VOLTAGE PRODUCTION DISTRIBUTION
24
17.5 Typical distribution of packaged units.
Percent of Amplifiers (%)
Percent of Units (%)
15.0
16
8
12.5 10.0 5.5 5.0 2.5
0 0
3.16 3.25 3.34 3.43
3.51 3.60
–150 –135 –120 –105 –90 –75 –60 –45 –30 –15 0 15 30 45 60 75 90 105 120 135 150
0 3.69 3.78
Noise (nV/√Hz)
Offset Voltage (µV)
OFFSET VOLTAGE DRIFT PRODUCTION DISTRIBUTION
WARM-UP OFFSET VOLTAGE DRIFT
12
10 8 Offset Voltage Change (µV)
Percent of Amplifiers (%)
Typical distribution of packaged units.
8
4
6 4 2 0 –2 –4 –6 –8
0
–10 0
0.5
1.0
0
1.5
100
150
200
250
300
Time from Power Supply Turn-On (s)
Offset Voltage Drift (µV)/°C
6
50
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
AOL, CMRR, PSRR vs TEMPERATURE
AOL, CMRR, PSRR vs TEMPERATURE 160
160
AOL
AOL, CMRR, PSRR (dB)
AOL, CMRR, PSRR (dB)
CMRR
140 130 PSRR
120 110 100 90 80
OPA227
70 60 –75
–50
AOL
150
150
CMRR
140 130 PSRR
120 110 100 90 80
OPA228
70 –25
0
25
50
75
100
60 –75
125
–50
–25
0
Short-Circuit Current (mA)
Input Bias Current (nA)
75
100
125
60
1.5 1.0 0.5 0 –0.5 –1.0 –1.5
–40 –20
0
20
40
60
80
50 40 30 20 10 0 –75
100 120 140
–ISC
+ISC
–50
–25
0
25
50
75
100
125
Temperature (°C)
Temperature (°C)
QUIESCENT CURRENT vs SUPPLY VOLTAGE
QUIESCENT CURRENT vs TEMPERATURE 3.8 ±18V ±15V ±12V ±10V
4.5
4.0
±5V ±2.5V
3.5
3.0
Quiescent Current (mA)
5.0
Quiescent Current (mA)
50
SHORT-CIRCUIT CURRENT vs TEMPERATURE
INPUT BIAS CURRENT vs TEMPERATURE 2.0
–2.0 –60
25
Temperature (°C)
Temperature (°C)
3.6
3.4
3.2
3.0
2.8
2.5 –60 –40
–20
0
20
40
60
80
0
100 120 140
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
2
4
6
8
10
12
14
16
18
20
Supply Voltage (±V)
Temperature (°C)
www.ti.com
7
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SLEW RATE vs TEMPERATURE
SLEW RATE vs TEMPERATURE
3.0
12
OPA227
OPA228 10
Positive Slew Rate Negative Slew Rate
Slew Rate (µV/V)
Slew Rate (µV/V)
2.5 2.0 1.5 1.0
8 6 4
RLOAD = 2kΩ CLOAD = 100pF
0.5 0
0 –75
–50
–25
0
25
50
75
100
125
–75
–50
–25
0
75
CHANGE IN INPUT BIAS CURRENT vs POWER SUPPLY VOLTAGE
CHANGE IN INPUT BIAS CURRENT vs COMMON-MODE VOLTAGE
100
125
1.5
1.0
Curve shows normalized change in bias current with respect to VCM = 0V. Typical IB may range from –2nA to +2nA at VCM = 0V.
1.0 0.5 ∆IB (nA)
0.5 0 –0.5
VS = ±15V
0 –0.5
VS = ±5V
–1.0 –1.0
–1.5
–1.5
–2.0 0
5
10
15
20
25
30
35
–15
40
–10
–5
0
5
10
15
Common-Mode Voltage (V)
Supply Voltage (V)
OUTPUT VOLTAGE SWING vs OUTPUT CURRENT
SETTLING TIME vs CLOSED-LOOP GAIN 15
100
VS = ±15V, 10V Step CL = 1500pF RL = 2kΩ
Output Voltage Swing (V)
Settling Time (µs)
50
Temperature (°C)
Curve shows normalized change in bias current with respect to VS = ±10V. Typical IB may range from –2nA to +2nA at VS = ±10V.
1.5
OPA227 0.01%
10
0.1%
OPA228 0.01%
0.1%
1 ±1
±10
±100
V+
14
(V+) –1V
13
(V+) –2V
12
–40°C
125°C 85°C 25°C
11 10 –10
–55°C
85°C
–11
(V+) –3V
–55°C
125°C
–12
(V–) +3V
–40°C 25°C
–13
(V–) +2V
–14
(V–) +1V
–15
V– 0
10
20
30
40
50
60
Output Current (mA)
Gain (V/V)
8
25
Temperature (°C)
2.0
∆IB (nA)
RLOAD = 2kΩ CLOAD = 100pF
2
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SMALL-SIGNAL OVERSHOOT vs LOAD CAPACITANCE
MAXIMUM OUTPUT VOLTAGE vs FREQUENCY 30
70
VS = ±15V
OPA227
OPA227 60
Gain = +10
50
20
Overshoot (%)
Output Voltage (Vp-p)
25
15 VS = ±5V
10
40 30 20
5 0
Gain = –10
Gain = –1 Gain = +1
10 0
1k
10k
100k
1M
10M
1
10
100
1k
10k
Frequency (Hz)
Load Capacitance (pF)
LARGE-SIGNAL STEP RESPONSE G = –1, CL = 1500pF
SMALL-SIGNAL STEP RESPONSE G = +1, CL = 1000pF
OPA227
100k
2V/div
25mV/div
OPA227
400ns/div
5µs/div
SMALL-SIGNAL STEP RESPONSE G = +1, CL = 5pF
25mV/div
OPA227
400ns/div
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
9
TYPICAL PERFORMANCE CURVES (CONT) At TA = +25°C, RL = 10kΩ, and VS = ±15V, unless otherwise noted.
SMALL-SIGNAL OVERSHOOT vs LOAD CAPACITANCE
MAXIMUM OUTPUT VOLTAGE vs FREQUENCY 30
70
VS = ±15V
OPA228
OPA228 60 50
20
Overshoot (%)
Output Voltage (Vp-p)
25
15 VS = ±5V
10
G = –100 40 30 G = +100 20 G = ±10
5
10 0
0 1k
10k
100k
1M
1
10M
10
Frequency (Hz)
100
1k
10k
100k
Load Capacitance (pF)
SMALL-SIGNAL STEP RESPONSE G = +10, CL = 1000pF, RL = 1.8kΩ
LARGE-SIGNAL STEP RESPONSE G = –10, CL = 100pF
OPA228
5V/div
200mV/div
OPA228
500ns/div
2µs/div
SMALL-SIGNAL STEP RESPONSE G = +10, CL = 5pF, RL = 1.8kΩ
200mV/div
OPA228
500ns/div
10
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
APPLICATIONS INFORMATION
Trim range exceeds offset voltage specification
V+
The OPA227 and OPA228 series are precision op amps with very low noise. The OPA227 series is unity-gain stable with a slew rate of 2.3V/µs and 8MHz bandwidth. The OPA228 series is optimized for higher-speed applications with gains of 5 or greater, featuring a slew rate of 10V/µs and 33MHz bandwidth. Applications with noisy or high impedance power supplies may require decoupling capacitors close to the device pins. In most cases, 0.1µF capacitors are adequate.
0.1µF 20kΩ 7
2
1 8
OPA227 6
3
OPA227 and OPA228 single op amps only. Use offset adjust pins only to null offset voltage of op amp. See text.
4
0.1µF V–
OFFSET VOLTAGE AND DRIFT The OPA227 and OPA228 series have very low offset voltage and drift. To achieve highest dc precision, circuit layout and mechanical conditions should be optimized. Connections of dissimilar metals can generate thermal potentials at the op amp inputs which can degrade the offset voltage and drift. These thermocouple effects can exceed the inherent drift of the amplifier and ultimately degrade its performance. The thermal potentials can be made to cancel by assuring that they are equal at both input terminals. In addition: • Keep thermal mass of the connections made to the two input terminals similar. • Locate heat sources as far as possible from the critical input circuitry. • Shield op amp and input circuitry from air currents such as those created by cooling fans.
FIGURE 1. OPA227 Offset Voltage Trim Circuit. amp. This adjustment should not be used to compensate for offsets created elsewhere in the system since this can introduce additional temperature drift. INPUT PROTECTION Back-to-back diodes (see Figure 2) are used for input protection on the OPA227 and OPA228. Exceeding the turn-on threshold of these diodes, as in a pulse condition, can cause current to flow through the input protection diodes due to the amplifier’s finite slew rate. Without external current-limiting resistors, the input devices can be destroyed. Sources of high input current can cause subtle damage to the amplifier. Although the unit may still be functional, important parameters such as input offset voltage, drift, and noise may shift.
OPERATING VOLTAGE OPA227 and OPA228 series op amps operate from ±2.5V to ±18V supplies with excellent performance. Unlike most op amps which are specified at only one supply voltage, the OPA227 series is specified for real-world applications; a single set of specifications applies over the ±5V to ±15V supply range. Specifications are assured for applications between ±5V and ±15V power supplies. Some applications do not require equal positive and negative output voltage swing. Power supply voltages do not need to be equal. The OPA227 and OPA228 series can operate with as little as 5V between the supplies and with up to 36V between the supplies. For example, the positive supply could be set to 25V with the negative supply at –5V or vice-versa. In addition, key parameters are assured over the specified temperature range, –40°C to +85°C. Parameters which vary significantly with operating voltage or temperature are shown in the Typical Performance Curves. OFFSET VOLTAGE ADJUSTMENT The OPA227 and OPA228 series are laser-trimmed for very low offset and drift so most applications will not require external adjustment. However, the OPA227 and OPA228 (single versions) provide offset voltage trim connections on pins 1 and 8. Offset voltage can be adjusted by connecting a potentiometer as shown in Figure 1. This adjustment should be used only to null the offset of the op
RF 500Ω
–
OPA227 Input
+
FIGURE 2. Pulsed Operation. When using the OPA227 as a unity-gain buffer (follower), the input current should be limited to 20mA. This can be accomplished by inserting a feedback resistor or a resistor in series with the source. Sufficient resistor size can be calculated: RX = VS/20mA – RSOURCE where RX is either in series with the source or inserted in the feedback path. For example, for a 10V pulse (VS = 10V), total loop resistance must be 500Ω. If the source impedance is large enough to sufficiently limit the current on its own, no additional resistors are needed. The size of any external resistors must be carefully chosen since they will increase noise. See the Noise Performance section of this data sheet for further information on noise calculation. Figure 2 shows an example implementing a currentlimiting feedback resistor.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
Output
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11
INPUT BIAS CURRENT CANCELLATION
NOISE PERFORMANCE
The input bias current of the OPA227 and OPA228 series is internally compensated with an equal and opposite cancellation current. The resulting input bias current is the difference between with input bias current and the cancellation current. The residual input bias current can be positive or negative.
Figure 4 shows total circuit noise for varying source impedances with the op amp in a unity-gain configuration (no feedback resistor network, therefore no additional noise contributions). Two different op amps are shown with total circuit noise calculated. The OPA227 has very low voltage noise, making it ideal for low source impedances (less than 20kΩ). A similar precision op amp, the OPA277, has somewhat higher voltage noise but lower current noise. It provides excellent noise performance at moderate source impedance (10kΩ to 100kΩ). Above 100kΩ, a FET-input op amp such as the OPA132 (very low current noise) may provide improved performance. The equation is shown for the calculation of the total circuit noise. Note that en = voltage noise, in = current noise, RS = source impedance, k = Boltzmann’s constant = 1.38 • 10–23 J/K and T is temperature in K. For more details on calculating noise, see the insert titled “Basic Noise Calculations.”
When the bias current is cancelled in this manner, the input bias current and input offset current are approximately equal. A resistor added to cancel the effect of the input bias current (as shown in Figure 3) may actually increase offset and noise and is therefore not recommended. Conventional Op Amp Configuration R2 R1
Not recommended for OPA227
RB = R2 || R1
Op Amp
VOLTAGE NOISE SPECTRAL DENSITY vs SOURCE RESISTANCE
External Cancellation Resistor Votlage Noise Spectral Density, E0 Typical at 1k (V/√Hz)
1.00+03
Recommended OPA227 Configuration R2 R1
OPA227
EO
OPA227
RS
1.00E+02
OPA277
OPA277
Resistor Noise
OPA227
1.00E+01
Resistor Noise EO2 = en2 + (in RS)2 + 4kTRS 1.00E+00
No cancellation resistor. See text.
100
1k
10k
100k
10M
Source Resistance, RS (Ω)
FIGURE 4. Noise Performance of the OPA227 in UnityGain Buffer Configuration.
FIGURE 3. Input Bias Current Cancellation.
BASIC NOISE CALCULATIONS Design of low noise op amp circuits requires careful consideration of a variety of possible noise contributors: noise from the signal source, noise generated in the op amp, and noise from the feedback network resistors. The total noise of the circuit is the root-sum-square combination of all noise components. The resistive portion of the source impedance produces thermal noise proportional to the square root of the resistance. This function is shown plotted in Figure 4. Since the source impedance is usually fixed, select the op amp and the feedback resistors to minimize their contribution to the total noise. Figure 4 shows total noise for varying source impedances with the op amp in a unity-gain configuration (no feedback resistor network and therefore no additional noise contributions). The operational amplifier itself contributes both a voltage noise component and a current
12
noise component. The voltage noise is commonly modeled as a time-varying component of the offset voltage. The current noise is modeled as the time-varying component of the input bias current and reacts with the source resistance to create a voltage component of noise. Consequently, the lowest noise op amp for a given application depends on the source impedance. For low source impedance, current noise is negligible and voltage noise generally dominates. For high source impedance, current noise may dominate. Figure 5 shows both inverting and noninverting op amp circuit configurations with gain. In circuit configurations with gain, the feedback network resistors also contribute noise. The current noise of the op amp reacts with the feedback resistors to create additional noise components. The feedback resistor values can generally be chosen to make these noise sources negligible. The equations for total noise are shown for both configurations. OPA227, 2227, 4227 OPA228, 2228, 4228
www.ti.com
SBOS110A
Noise in Noninverting Gain Configuration R2
Noise at the output: 2
R R 2 2 E O 2 = 1 + 2 e n 2 + e12 + e 2 2 + (i n R 2 ) + e S 2 + (i n R S ) 1 + 2 R1 R1
R1 EO
RS
VS
2
R Where eS = √4kTRS • 1 + 2 = thermal noise of RS R1 R e1 = √4kTR1 • 2 R1
= thermal noise of R1
e2 = √4kTR2
= thermal noise of R2
Noise in Inverting Gain Configuration R2
Noise at the output: 2
R1
RS
EO
VS
R2 2 2 2 2 2 E O 2 = 1 + e n + e1 + e 2 + (i n R 2 ) + e S R1 + R S
R2 Where eS = √4kTRS • = thermal noise of RS R1 + R S R2 e1 = √4kTR1 • = thermal noise of R1 R1 + R S
e2 = √4kTR2
= thermal noise of R2
For the OPA227 and OPA228 series op amps at 1kHz, en = 3nV/√Hz and in = 0.4pA/√Hz.
FIGURE 5. Noise Calculation in Gain Configurations.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
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13
R1 2MΩ
R2 2MΩ
R8 402kΩ
R11 178kΩ
R3 1kΩ
R4 9.09kΩ
C4 22nF
C6 10nF
R6 40.2kΩ C2 1µF
C1 1µF
U1
C3 0.47µF
(OPA227) Input from Device Under Test
R7 97.6kΩ
R9 178kΩ
2 3
U2
R10 226kΩ
2
6
(OPA227)
C5 0.47µF
3
U3
6
VOUT
(OPA227)
R5 634kΩ
FIGURE 6. 0.1Hz to 10Hz Bandpass Filter Used to Test Wideband Noise of the OPA227 and OPA228 Series. USING THE OPA228 IN LOW GAINS The OPA228 family is intended for applications with signal gains of 5 or greater, but it is possible to take advantage of their high speed in lower gains. Without external compensation, the OPA228 has sufficient phase margin to maintain stability in unity gain with purely resistive loads. However, the addition of load capacitance can reduce the phase margin and destabilize the op amp.
22pF
100kΩ 10Ω
2 3
OPA227
6
VOUT
Device Under Test
FIGURE 7. Noise Test Circuit. Figure 6 shows the 0.1Hz 10Hz bandpass filter used to test the noise of the OPA227 and OPA228. The filter circuit was designed using Texas Instruments’ FilterPro software (available at www.ti.com). Figure 7 shows the configuration of the OPA227 and OPA228 for noise testing.
14
A variety of compensation techniques have been evaluated specifically for use with the OPA228. The recommended configuration consists of an additional capacitor (CF) in parallel with the feedback resistance, as shown in Figures 8 and 11. This feedback capacitor serves two purposes in compensating the circuit. The op amp’s input capacitance and the feedback resistors interact to cause phase shift that can result in instability. CF compensates the input capacitance, minimizing peaking. Additionally, at high frequencies, the closed-loop gain of the amplifier is strongly influenced by the ratio of the input capacitance and the feedback capacitor. Thus, CF can be selected to yield good stability while maintaining high speed.
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
Without external compensation, the noise specification of the OPA228 is the same as that for the OPA227 in gains of 5 or greater. With the additional external compensation, the output noise of the of the OPA228 will be higher. The amount of noise increase is directly related to the increase in high frequency closed-loop gain established by the CIN/ CF ratio. Figures 8 and 11 show the recommended circuit for gains of +2 and –2, respectively. The figures suggest approximate
values for CF. Because compensation is highly dependent on circuit design, board layout, and load conditions, CF should be optimized experimentally for best results. Figures 9 and 10 show the large- and small-signal step responses for the G = +2 configuration with 100pF load capacitance. Figures 12 and 13 show the large- and smallsignal step responses for the G = –2 configuration with 100pF load capacitance.
15pF
22pF
1kΩ
2kΩ
2kΩ
2kΩ
OPA228
OPA228 2kΩ
2kΩ
100pF
FIGURE 11. Compensation for OPA228 for G = –2.
5mV/div
5mV/div
FIGURE 8. Compensation of the OPA228 for G =+2.
OPA228
OPA228
400ns/div
400ns/div
FIGURE 12. Large-Signal Step Response, G = –2, CLOAD = 100pF, Input Signal = 5Vp-p.
25mV/div
25mV/div
FIGURE 9. Large-Signal Step Response, G = +2, CLOAD = 100pF, Input Signal = 5Vp-p.
OPA228
OPA228
200ns/div
200ns/div
FIGURE 10. Small-Signal Step Response, G = +2, CLOAD = 100pF, Input Signal = 50mVp-p.
FIGURE 13. Small-Signal Step Response, G = –2, CLOAD = 100pF, Input Signal = 50mVp-p.
OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
100pF
www.ti.com
15
1.1kΩ 1.43kΩ
2.2nF
dc Gain = 1
330pF 1.1kΩ
1.65kΩ
VIN
1.43kΩ
1.91kΩ
OPA227
33nF
2.21kΩ
OPA227
68nF
VOUT 10nF
fN = 13.86kHz
fN = 20.33kHz
Q = 1.186
Q = 4.519
f = 7.2kHz
FIGURE 14. Three-Pole, 20kHz Low Pass, 0.5dB Chebyshev Filter.
20pF 0.1µF
100Ω
TTL INPUT
GAIN
“1” “0”
+1 –1
100kΩ
9.76kΩ
500Ω
2 3
OPA227
6
Output
10kΩ
Input D1
Dexter 1M Thermopile Detector
NOTE: Use metal film resistors and plastic film capacitor. Circuit must be well shielded to achieve low noise.
D2
TTL In
FIGURE 15. Long-Wavelength Infrared Detector Amplifier.
16
2 4.99kΩ S1 S2
3
6
OPA227
Output
8 1 4.75kΩ
Responsivity ≈ 2.5 x 104V/W Output Noise ≈ 30µVrms, 0.1Hz to 10Hz
Balance Trim
4.75kΩ
1kΩ
DG188 Offset Trim
+VCC
FIGURE 16. High Performance Synchronous Demodulator.
OPA227, 2227, 4227 OPA228, 2228, 4228 www.ti.com
SBOS110A
+15V
0.1µF 1kΩ
1kΩ Audio In
1/2 OPA2227 200Ω To Headphone
200Ω
1/2 OPA2227 This application uses two op amps in parallel for higher output current drive.
0.1µF
–15V
FIGURE 17. Headphone Amplifier.
Bass Tone Control R1 7.5kΩ
R2 50kΩ 3
1
CW
2
R3 7.5kΩ
R10 100kΩ
Midrange Tone Control C1 940pF
R4 2.7kΩ VIN
R5 50kΩ 3
CW
1 2
R6 2.7kΩ C2 0.0047µF
Treble Tone Control R7 7.5kΩ
R8 50kΩ 3
CW
1 2
R9 7.5kΩ
C3 680pF
R11 100kΩ
2 3
OPA227
6
VOUT
FIGURE 18. Three-Band ActiveTone Control (bass, midrange and treble). OPA227, 2227, 4227 OPA228, 2228, 4228 SBOS110A
www.ti.com
17
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
PACKAGING INFORMATION Orderable Device
Status (1)
Package Type
Package Drawing
Pins Package Eco Plan (2) Qty
OPA2227P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2227U
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5E4
ACTIVE
SOIC
D
8
2500
CU NIPDAU
Level-3-260C-168 HR
OPA2227U/2K5G4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UA/2K5E4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UAE4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UE4
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2227UG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA2228P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA2228U
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228U/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228UA
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA2228UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
Addendum-Page 1
Pb-Free (RoHS)
Lead/Ball Finish
MSL Peak Temp (3)
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
Orderable Device
Status (1)
Package Type
Package Drawing
Pins Package Eco Plan (2) Qty
OPA227PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA227U
ACTIVE
SOIC
D
8
100
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227U/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA/2K5
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UA/2K5G4
ACTIVE
SOIC
D
8
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA227UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228P
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PA
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PAG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228PG4
ACTIVE
PDIP
P
8
50
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA228U
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UA
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UA/2K5
ACTIVE
SOIC
D
8
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA228UAG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA228UG4
ACTIVE
SOIC
D
8
100
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227PA
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4227PAG4
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4227UA
ACTIVE
SOIC
D
14
58
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UA/2K5
ACTIVE
SOIC
D
14
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UA/2K5G4
ACTIVE
SOIC
D
14
2500 Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4227UAG4
ACTIVE
SOIC
D
14
58
Green (RoHS & no Sb/Br)
CU NIPDAU
Level-3-260C-168 HR
OPA4228PA
ACTIVE
PDIP
N
14
25
Green (RoHS & no Sb/Br)
CU NIPDAU
N / A for Pkg Type
OPA4228UA
ACTIVE
SOIC
D
14
58
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
OPA4228UA/2K5
ACTIVE
SOIC
D
14
2500
Pb-Free (RoHS)
CU NIPDAU
Level-3-260C-168 HR
Addendum-Page 2
Lead/Ball Finish
MSL Peak Temp (3)
PACKAGE OPTION ADDENDUM www.ti.com
8-Jan-2007
(1)
The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 3
MECHANICAL DATA MPDI001A – JANUARY 1995 – REVISED JUNE 1999
P (R-PDIP-T8)
PLASTIC DUAL-IN-LINE
0.400 (10,60) 0.355 (9,02) 8
5
0.260 (6,60) 0.240 (6,10)
1
4 0.070 (1,78) MAX 0.325 (8,26) 0.300 (7,62)
0.020 (0,51) MIN
0.015 (0,38) Gage Plane
0.200 (5,08) MAX Seating Plane
0.010 (0,25) NOM
0.125 (3,18) MIN
0.100 (2,54) 0.021 (0,53) 0.015 (0,38)
0.430 (10,92) MAX
0.010 (0,25) M
4040082/D 05/98 NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. Falls within JEDEC MS-001
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